Methods and apparatus for coupling and decoupling portions of a magnetic core

ABSTRACT

Aspects of the subject disclosure may include, regulating an alternating magnetic flux in a magnetic core having a first portion separable from a second portion of the magnetic core. The regulation of the alternating magnetic flux causes a coupling force between the first portion of the magnetic core and the second portion of the magnetic core. Responsive to detecting a signal, modifying the regulation of the alternating magnetic flux to reduce the coupling force between the first portion of the magnetic core and the second portion of the magnetic core. Other embodiments are disclosed.

FIELD OF THE DISCLOSURE

The subject disclosure relates to inductive power supplies.

BACKGROUND

As smart phones and other portable devices increasingly becomeubiquitous, and data usage increases, macrocell base station devices andexisting wireless infrastructure in turn require higher bandwidthcapability in order to address the increased demand. To provideadditional mobile bandwidth, small cell deployment is being pursued,with microcells and picocells providing coverage for much smaller areasthan traditional macrocells.

In addition, most homes and businesses have grown to rely on broadbanddata access for services such as voice, video and Internet browsing,etc. Broadband access networks include satellite, 4G or 5G wireless,power line communication, fiber, cable, and telephone networks.

BRIEF DESCRIPTION OF THE DRAWINGS

Reference will now be made to the accompanying drawings, which are notnecessarily drawn to scale, and wherein:

FIG. 1 is a block diagram illustrating an example, non-limitingembodiment of a guided-wave communications system in accordance withvarious aspects described herein.

FIG. 2 is a block diagram illustrating an example, non-limitingembodiment of a transmission device in accordance with various aspectsdescribed herein.

FIG. 3 is a graphical diagram illustrating an example, non-limitingembodiment of an electromagnetic field distribution in accordance withvarious aspects described herein.

FIG. 4 is a graphical diagram illustrating an example, non-limitingembodiment of an electromagnetic field distribution in accordance withvarious aspects described herein.

FIG. 5A is a graphical diagram illustrating an example, non-limitingembodiment of a frequency response in accordance with various aspectsdescribed herein.

FIG. 5B is a graphical diagram illustrating example, non-limitingembodiments of a longitudinal cross-section of an insulated wiredepicting fields of guided electromagnetic waves at various operatingfrequencies in accordance with various aspects described herein.

FIG. 6 is a graphical diagram illustrating an example, non-limitingembodiment of an electromagnetic field distribution in accordance withvarious aspects described herein.

FIG. 7 is a block diagram illustrating an example, non-limitingembodiment of an arc coupler in accordance with various aspectsdescribed herein.

FIG. 8 is a block diagram illustrating an example, non-limitingembodiment of an arc coupler in accordance with various aspectsdescribed herein.

FIG. 9A is a block diagram illustrating an example, non-limitingembodiment of a stub coupler in accordance with various aspectsdescribed herein.

FIG. 9B is a diagram illustrating an example, non-limiting embodiment ofan electromagnetic distribution in accordance with various aspectsdescribed herein.

FIG. 10 is a block diagram illustrating an example, non-limitingembodiment of a coupler and transceiver in accordance with variousaspects described herein.

FIG. 11 is a block diagram illustrating an example, non-limitingembodiment of a dual stub coupler in accordance with various aspectsdescribed herein.

FIG. 12 is a block diagram illustrating an example, non-limitingembodiment of a repeater system in accordance with various aspectsdescribed herein.

FIG. 13 illustrates a block diagram illustrating an example,non-limiting embodiment of a bidirectional repeater in accordance withvarious aspects described herein.

FIG. 14 is a block diagram illustrating an example, non-limitingembodiment of a waveguide system in accordance with various aspectsdescribed herein.

FIG. 15 is a block diagram illustrating an example, non-limitingembodiment of a guided-wave communications system in accordance withvarious aspects described herein.

FIGS. 16A & 16B are block diagrams illustrating an example, non-limitingembodiment of a system for managing a power grid communication system inaccordance with various aspects described herein.

FIG. 17A illustrates a flow diagram of an example, non-limitingembodiment of a method for detecting and mitigating disturbancesoccurring in a communication network of the system of FIGS. 16A and 16B.

FIG. 17B illustrates a flow diagram of an example, non-limitingembodiment of a method for detecting and mitigating disturbancesoccurring in a communication network of the system of FIGS. 16A and 16B.

FIG. 18A is a block diagram illustrating an example, non-limitingembodiment of a transmission medium for propagating guidedelectromagnetic waves.

FIG. 18B is a block diagram illustrating an example, non-limitingembodiment of bundled transmission media in accordance with variousaspects described herein.

FIG. 18C is a block diagram illustrating an example, non-limitingembodiment of exposed stubs from the bundled transmission media for useas antennas in accordance with various aspects described herein.

FIGS. 18D, 18E, 18F, 18G, 18H, 18I, 18J and 18K are block diagramsillustrating example, non-limiting embodiments of a waveguide device fortransmitting or receiving electromagnetic waves in accordance withvarious aspects described herein.

FIGS. 19A and 19B are block diagrams illustrating example, non-limitingembodiments of a dielectric antenna and corresponding gain and fieldintensity plots in accordance with various aspects described herein.

FIG. 19C is a block diagram illustrating an example, non-limitingembodiments of a dielectric antenna coupled to a lens in accordance withvarious aspects described herein.

FIG. 19D is a block diagram illustrating an example, non-limitingembodiment of near-field and far-field signals emitted by the dielectricantenna of FIG. 19G in accordance with various aspects described herein.

FIG. 19E is a block diagram of an example, non-limiting embodiment of adielectric antenna in accordance with various aspects described herein.

FIG. 19F is a block diagram of an example, non-limiting embodiment of anarray of dielectric antennas configurable for steering wireless signalsin accordance with various aspects described herein.

FIGS. 20A and 20B are block diagrams illustrating example, non-limitingembodiments of the transmission medium of FIG. 18A used for inducingguided electromagnetic waves on power lines supported by utility poles.

FIG. 20C is a block diagram of an example, non-limiting embodiment of acommunication network in accordance with various aspects describedherein.

FIG. 20D is a block diagram of an example, non-limiting embodiment of anantenna mount for use in a communication network in accordance withvarious aspects described herein.

FIG. 20E is a block diagram of an example, non-limiting embodiment of anantenna mount for use in a communication network in accordance withvarious aspects described herein.

FIG. 21A illustrates a flow diagram of an example, non-limitingembodiment of a method for transmitting downlink signals.

FIG. 21B illustrates a flow diagram of an example, non-limitingembodiment of a method for transmitting uplink signals.

FIG. 21C is a block diagram illustrating an example, non-limitingembodiment of electric field characteristics of a hybrid wave versus aGoubau wave in accordance with various aspects described herein.

FIG. 21D is a block diagram illustrating an example, non-limitingembodiment of mode sizes of hybrid waves at various operatingfrequencies in accordance with various aspects described herein.

FIGS. 22A and 22B are block diagrams illustrating example, non-limitingembodiments of a waveguide device for launching hybrid waves inaccordance with various aspects described herein.

FIGS. 23A, 23B, and 23C are block diagrams illustrating example,non-limiting embodiments of a waveguide device in accordance withvarious aspects described herein.

FIG. 24 is a block diagram illustrating an example, non-limitingembodiment of a waveguide device in accordance with various aspectsdescribed herein.

FIG. 25A is a block diagram illustrating an example, non-limitingembodiment of a waveguide device in accordance with various aspectsdescribed herein.

FIGS. 25B, 25C and 25D are block diagrams illustrating example,non-limiting embodiments of wave modes and electric field plots inaccordance with various aspects described herein.

FIG. 26 illustrates a flow diagram of an example, non-limitingembodiment of a method for managing electromagnetic waves.

FIG. 27 is a block diagram illustrating an example, non-limitingembodiment of substantially orthogonal wave modes in accordance withvarious aspects described herein.

FIG. 28 is a block diagram illustrating an example, non-limitingembodiment of an insulated conductor in accordance with various aspectsdescribed herein.

FIG. 29 is a block diagram illustrating an example, non-limitingembodiment of an uninsulated conductor in accordance with variousaspects described herein.

FIG. 30 is a block diagram illustrating an example, non-limitingembodiment of an oxide layer formed on the uninsulated conductor of FIG.25A in accordance with various aspects described herein.

FIG. 31 is a block diagram illustrating example, non-limitingembodiments of spectral plots in accordance with various aspectsdescribed herein.

FIG. 32 is a block diagram illustrating example, non-limitingembodiments of spectral plots in accordance with various aspectsdescribed herein.

FIG. 33 is a block diagram illustrating example, non-limitingembodiments for transmitting orthogonal wave modes in accordance withvarious aspects described herein.

FIG. 34 is a block diagram illustrating example, non-limitingembodiments for transmitting orthogonal wave modes in accordance withvarious aspects described herein.

FIG. 35 is a block diagram illustrating example, non-limitingembodiments for selectively receiving a wave mode in accordance withvarious aspects described herein.

FIG. 36 is a block diagram illustrating example, non-limitingembodiments for selectively receiving a wave mode in accordance withvarious aspects described herein.

FIG. 37 is a block diagram illustrating example, non-limitingembodiments for selectively receiving a wave mode in accordance withvarious aspects described herein.

FIG. 38 is a block diagram illustrating example, non-limitingembodiments for selectively receiving a wave mode in accordance withvarious aspects described herein.

FIG. 39 is a block diagram illustrating example, non-limitingembodiments of a polyrod antenna for transmitting wireless signals inaccordance with various aspects described herein.

FIG. 40 is a block diagram illustrating an example, non-limitingembodiment of electric field characteristics of transmitted signals froma polyrod antenna in accordance with various aspects described herein.

FIGS. 41 and 42 are block diagrams illustrating an example, non-limitingembodiment of a polyrod antenna array in accordance with various aspectsdescribed herein.

FIGS. 43A and 43B are block diagrams illustrating an example,non-limiting embodiment of an antenna, and electric fieldcharacteristics of transmitted signals from the antenna in accordancewith various aspects described herein.

FIG. 44A is a block diagram illustrating an example, non-limitingembodiment of a communication system in accordance with various aspectsdescribed herein.

FIG. 44B is a block diagram illustrating an example, non-limitingembodiment of a portion of the communication system of FIG. 44A inaccordance with various aspects described herein.

FIG. 44C is a graphical diagram illustrating an example, non-limitingembodiment of downlink and uplink communication techniques for enablinga base station to communicate with communication nodes in accordancewith various aspects described herein.

FIG. 44D is a graphical diagram illustrating an example, non-limitingembodiment of a frequency spectrum in accordance with various aspectsdescribed herein.

FIG. 44E is a graphical diagram illustrating an example, non-limitingembodiment of a frequency spectrum in accordance with various aspectsdescribed herein.

FIG. 45 is a block diagram illustrating an example, non-limitingembodiment of a communication system that utilizes beam steering inaccordance with various aspects described herein.

FIGS. 46A, 46B, 46C, 46D, 46E, 46F, 46G, 46H, and 46I are graphicaldiagrams illustrating examples, components of an inductive power supplyand graphical plots in accordance with various aspects described herein.

FIG. 46J is a graphical diagram illustrating an example, a resonator toenhance a magnetic flux in a core of an inductive power supply inaccordance with various aspects described herein.

FIG. 46K is a graphical diagram illustrating an example, a voltagewaveform generator to enhance a magnetic flux in a core of an inductivepower supply in accordance with various aspects described herein.

FIG. 46L is a graphical diagram illustrating an example, a voltagewaveform produced by a voltage waveform generator to enhance a magneticflux in a core of an inductive power supply in accordance with variousaspects described herein.

FIG. 46M is a graphical diagram illustrating an example, animplementation of a voltage waveform generator to enhance a magneticflux in a core of an inductive power supply in accordance with variousaspects described herein.

FIG. 46N illustrates a flow diagram of, an example, non-limitingembodiment of a method for enhancing a magnetic flux in a core of aninductive power supply accordance with various aspects described herein.

FIG. 46O is a graphical diagram illustrating, an example, non-limitingembodiment of an implementation of a voltage waveform generator toenhance a magnetic flux in a core of an inductive power supply inaccordance with various aspects described herein.

FIG. 46P illustrates a flow diagram of, an example, non-limitingembodiment of a method for enhancing a magnetic flux in a core of aninductive power supply accordance with various aspects described herein.

FIGS. 46Q1 and 46Q2 are graphical diagrams illustrating, example,non-limiting embodiments of a housing assembly for containing aninductive supply.

FIG. 47 is a block diagram illustrating an example, non-limitingembodiment of a communications network in accordance with variousaspects described herein.

FIG. 48 is a block diagram illustrating an example, non-limitingembodiment of a virtualized communication network in accordance withvarious aspects described herein.

FIG. 49 is a block diagram of an example, non-limiting embodiment of acomputing environment in accordance with various aspects describedherein.

FIG. 50 is a block diagram of an example, non-limiting embodiment of amobile network platform in accordance with various aspects describedherein.

FIG. 51 is a block diagram of an example, non-limiting embodiment of acommunication device in accordance with various aspects describedherein.

DETAILED DESCRIPTION

One or more embodiments are now described with reference to thedrawings, wherein like reference numerals are used to refer to likeelements throughout the drawings. In the following description, forpurposes of explanation, numerous details are set forth in order toprovide a thorough understanding of the various embodiments. It isevident, however, that the various embodiments can be practiced withoutthese details (and without applying to any particular networkedenvironment or standard).

In an embodiment, a guided wave communication system is presented forsending and receiving communication signals such as data or othersignaling via guided electromagnetic waves. The guided electromagneticwaves include, for example, surface waves or other electromagnetic wavesthat are bound to or guided by a transmission medium as describedherein. It will be appreciated that a variety of transmission media canbe utilized with guided wave communications without departing fromexample embodiments. Examples of such transmission media can include oneor more of the following, either alone or in one or more combinations:wires, whether insulated or not, and whether single-stranded ormulti-stranded; conductors of other shapes or configurations includingunshielded twisted pair cables including single twisted pairs, Category5e and other twisted pair cable bundles, other wire bundles, cables,rods, rails, pipes; non-conductors such as dielectric pipes, rods,rails, or other dielectric members; combinations of conductors anddielectric materials such as coaxial cables; or other guided wavetransmission media.

The inducement of guided electromagnetic waves that propagate along atransmission medium can be independent of any electrical potential,charge or current that is injected or otherwise transmitted through thetransmission medium as part of an electrical circuit. For example, inthe case where the transmission medium is a wire, it is to beappreciated that while a small current in the wire may be formed inresponse to the propagation of the electromagnetic waves guided alongthe wire, this can be due to the propagation of the electromagnetic wavealong the wire surface, and is not formed in response to electricalpotential, charge or current that is injected into the wire as part ofan electrical circuit. The electromagnetic waves traveling along thewire therefore do not require an electrical circuit (i.e., ground orother electrical return path) to propagate along the wire surface. Thewire therefore is a single wire transmission line that is not part of anelectrical circuit. For example, electromagnetic waves can propagatealong a wire configured as an electrical open circuit. Also, in someembodiments, a wire is not necessary, and the electromagnetic waves canpropagate along a single line transmission medium that is not a wireincluding a single line transmission medium that is conductorless.Accordingly, electromagnetic waves can propagate along a physicaltransmission medium without requiring an electrical return path

More generally, “guided electromagnetic waves” or “guided waves” asdescribed by the subject disclosure are affected by the presence of aphysical object that is at least a part of the transmission medium(e.g., a bare wire or other conductor, a dielectric including adielectric core without a conductive shield and/or without an innerconductor, an insulated wire, a conduit or other hollow element whetherconductive or not, a bundle of insulated wires that is coated, coveredor surrounded by a dielectric or insulator or other wire bundle, oranother form of solid, liquid or otherwise non-gaseous transmissionmedium) so as to be at least partially bound to or guided by thephysical object and so as to propagate along a transmission path of thephysical object. Such a physical object can operate as at least a partof a transmission medium that guides, by way of one or more interfacesof the transmission medium (e.g., an outer surface, inner surface, aninterior portion between the outer and the inner surfaces or otherboundary between elements of the transmission medium). In this fashion,a transmission medium may support multiple transmission paths overdifferent surfaces of the transmission medium. For example, a strandedcable or wire bundle may support electromagnetic waves that are guidedby the outer surface of the stranded cable or wire bundle, as well aselectromagnetic waves that are guided by inner cable surfaces betweentwo, three or more individual strands or wires within the stranded cableor wire bundle. For example, electromagnetic waves can be guided withininterstitial areas of a stranded cable, insulated twisted pair wires, ora wire bundle. The guided electromagnetic waves of the subjectdisclosure are launched from a sending (transmitting) device andpropagate along the transmission medium for reception by at least onereceiving device. The propagation of guided electromagnetic waves, cancarry energy, data and/or other signals along the transmission path fromthe sending device to the receiving device.

As used herein the term “conductor” (based on a definition of the term“conductor” from IEEE 100, the Authoritative Dictionary of IEEEStandards Terms, 7^(th) Edition, 2000) means a substance or body thatallows a current of electricity to pass continuously along it. The terms“insulator”, “conductorless” or “nonconductor” (based on a definition ofthe term “insulator” from IEEE 100, the Authoritative Dictionary of IEEEStandards Terms, 7^(th) Edition, 2000) means a device or material inwhich electrons or ions cannot be moved easily. It is possible for aninsulator, or a conductorless or nonconductive material to be intermixedintentionally (e.g., doped) or unintentionally into a resultingsubstance with a small amount of another material having the propertiesof a conductor. However, the resulting substance may remainsubstantially resistant to a flow of a continuous electrical currentalong the resulting substance. Furthermore, a conductorless member suchas a dielectric rod or other conductorless core lacks an inner conductorand a conductive shield. As used herein, the term “eddy current” (basedon a definition of the term “conductor” from IEEE 100, the AuthoritativeDictionary of IEEE Standards Terms, 7^(th) Edition, 2000) means acurrent that circulates in a metallic material as a result ofelectromotive forces induced by a variation of magnetic flux. Althoughit may be possible for an insulator, conductorless or nonconductivematerial in the foregoing embodiments to allow eddy currents thatcirculate within the doped or intermixed conductor and/or a very smallcontinuous flow of an electrical current along the extent of theinsulator, conductorless or nonconductive material, any such continuousflow of electrical current along such an insulator, conductorless ornonconductive material is de minimis compared to the flow of anelectrical current along a conductor. Accordingly, in the subjectdisclosure an insulator, and a conductorless or nonconductor materialare not considered to be a conductor. The term “dielectric” means aninsulator that can be polarized by an applied electric field. When adielectric is placed in an electric field, electric charges do notcontinuously flow through the material as they do in a conductor, butonly slightly shift from their average equilibrium positions causingdielectric polarization. The terms “conductorless transmission medium ornon-conductor transmission medium” can mean a transmission mediumconsisting of any material (or combination of materials) that may or maynot contain one or more conductive elements but lacks a continuousconductor between the sending and receiving devices along theconductorless transmission medium or non-conductor transmissionmedium—similar or identical to the aforementioned properties of aninsulator, conductorless or nonconductive material.

Unlike free space propagation of wireless signals such as unguided (orunbounded) electromagnetic waves that decrease in intensity inversely bythe square of the distance traveled by the unguided electromagneticwaves, guided electromagnetic waves can propagate along a transmissionmedium with less loss in magnitude per unit distance than experienced byunguided electromagnetic waves.

Unlike electrical signals, guided electromagnetic waves can propagatealong different types of transmission media from a sending device to areceiving device without requiring a separate electrical return pathbetween the sending device and the receiving device. As a consequence,guided electromagnetic waves can propagate from a sending device to areceiving device along a conductorless transmission medium including atransmission medium having no conductive components (e.g., a dielectricstrip, rod, or pipe), or via a transmission medium having no more than asingle conductor (e.g., a single bare wire or insulated wire configuredin an open electrical circuit). Even if a transmission medium includesone or more conductive components and the guided electromagnetic wavespropagating along the transmission medium generate currents that flow inthe one or more conductive components in a direction of the guidedelectromagnetic waves, such guided electromagnetic waves can propagatealong the transmission medium from a sending device to a receivingdevice without requiring a flow of opposing currents on an electricalreturn path between the sending device and the receiving device (i.e.,in an electrical open circuit configuration).

In a non-limiting illustration, consider electrical systems thattransmit and receive electrical signals between sending and receivingdevices by way of conductive media. Such systems generally rely on anelectrical forward path and an electrical return path. For instance,consider a coaxial cable having a center conductor and a ground shieldthat are separated by an insulator. Typically, in an electrical system afirst terminal of a sending (or receiving) device can be connected tothe center conductor, and a second terminal of the sending (orreceiving) device can be connected to the ground shield or other secondconductor. If the sending device injects an electrical signal in thecenter conductor via the first terminal, the electrical signal willpropagate along the center conductor causing forward currents in thecenter conductor, and return currents in the ground shield or othersecond conductor. The same conditions apply for a two terminal receivingdevice.

In contrast, consider a guided wave communication system such asdescribed in the subject disclosure, which can utilize differentembodiments of a transmission medium (including among others a coaxialcable) for transmitting and receiving guided electromagnetic waveswithout requiring an electrical return path. In one embodiment, forexample, the guided wave communication system of the subject disclosurecan be configured to induce guided electromagnetic waves that propagatealong an outer surface of a coaxial cable. Although the guidedelectromagnetic waves can cause forward currents on the ground shield,the guided electromagnetic waves do not require return currents on, forexample, the center conductor to enable the guided electromagnetic wavesto propagate along the outer surface of the coaxial cable. The same canbe said of other transmission media used by a guided wave communicationsystem for the transmission and reception of guided electromagneticwaves. For example, guided electromagnetic waves induced by the guidedwave communication system on a bare wire, an insulated wire, or adielectric transmission medium (e.g., a dielectric core with noconductive materials), can propagate along the bare wire, the insulatedbare wire, or the dielectric transmission medium without requiringreturn currents on an electrical return path.

Consequently, electrical systems that require forward and returnconductors for carrying corresponding forward and reverse currents onconductors to enable the propagation of electrical signals injected by asending device are distinct from guided wave systems that induce guidedelectromagnetic waves on an interface of a transmission medium withoutrequiring an electrical return path to enable the propagation of theguided electromagnetic waves along the interface of the transmissionmedium. It is also noted that a transmission medium having an electricalreturn path (e.g., ground) for purposes of conducting currents (e.g., apower line) can be used to contemporaneously propagate electromagneticwaves along the transmission medium. However, the propagation of theelectromagnetic waves is not dependent on the electrical currentsflowing through the transmission medium. For example, if the electricalcurrents flowing through the transmission medium stop flowing for anyreason (e.g., a power outage), electromagnetic waves propagating alongthe transmission medium can continue to propagate without interruption.

It is further noted that guided electromagnetic waves as described inthe subject disclosure can have an electromagnetic field structure thatlies primarily or substantially on an outer surface of a transmissionmedium so as to be bound to or guided by the outer surface of thetransmission medium and so as to propagate non-trivial distances on oralong the outer surface of the transmission medium. In otherembodiments, guided electromagnetic waves can have an electromagneticfield structure that substantially lies above an outer surface of atransmission medium, but is nonetheless bound to or guided by thetransmission medium and so as to propagate non-trivial distances on oralong the transmission medium. In other embodiments, guidedelectromagnetic waves can have an electromagnetic field structure thathas a field strength that is de minimis at the outer surface, below theouter surface, and/or in proximity to the outer surface of atransmission medium, but is nonetheless bound to or guided by thetransmission medium and so as to propagate non-trivial distances alongthe transmission medium. In other embodiments, guided electromagneticwaves can have an electromagnetic field structure that lies primarily orsubstantially below an outer surface of a transmission medium so as tobe bound to or guided by an inner material of the transmission medium(e.g., dielectric material) and so as to propagate non-trivial distanceswithin the inner material of the transmission medium. In otherembodiments, guided electromagnetic waves can have an electromagneticfield structure that lies within a region that is partially below andpartially above an outer surface of a transmission medium so as to bebound to or guided by this region of the transmission medium and so asto propagate non-trivial distances along this region of the transmissionmedium. It will be appreciated that electromagnetic waves that propagatealong a transmission medium or are otherwise guided by a transmissionmedium (i.e., guided electromagnetic waves) can have an electric fieldstructure such as described in one or more of the foregoing embodiments.The desired electromagnetic field structure in an embodiment may varybased upon a variety of factors, including the desired transmissiondistance, the characteristics of the transmission medium itself,environmental conditions/characteristics outside of the transmissionmedium (e.g., presence of rain, fog, atmospheric conditions, etc.), andcharacteristics of an electromagnetic wave that are configurable by alauncher as will be described below (e.g., configurable wave mode,configurable electromagnetic field structure, configurable polarity,configurable wavelength, configurable bandwidth, and so on).

Various embodiments described herein relate to coupling devices, thatcan be referred to as “waveguide coupling devices”, “waveguide couplers”or more simply as “couplers”, “coupling devices” or “launchers” forlaunching and/or receiving/extracting guided electromagnetic waves toand from a transmission medium, wherein a wavelength of the guidedelectromagnetic waves can be small compared to one or more dimensions ofthe coupling device and/or the transmission medium such as thecircumference of a wire or other cross sectional dimension. Suchelectromagnetic waves can operate at millimeter wave frequencies (e.g.,30 to 300 GHz), or lower than microwave frequencies such as 300 MHz to30 GHz. Electromagnetic waves can be induced to propagate along atransmission medium by a coupling device, such as: a strip, arc or otherlength of dielectric material; a millimeter wave integrated circuit(MMIC), a horn, monopole, dipole, rod, slot, patch, planar or otherantenna; an array of antennas; a magnetic resonant cavity or otherresonant coupler; a coil, a strip line, a coaxial waveguide, a hollowwaveguide, or other waveguide and/or other coupling device. Inoperation, the coupling device receives an electromagnetic wave from atransmitter or transmission medium. The electromagnetic field structureof the electromagnetic wave can be carried below an outer surface of thecoupling device, substantially on the outer surface of the couplingdevice, within a hollow cavity of the coupling device, can be radiatedfrom a coupling device or a combination thereof. When the couplingdevice is in close proximity to a transmission medium, at least aportion of an electromagnetic wave couples to or is bound to thetransmission medium, and continues to propagate as guidedelectromagnetic waves along the transmission medium. In a reciprocalfashion, a coupling device can receive or extract at least a portion ofthe guided electromagnetic waves from a transmission medium and transferthese electromagnetic waves to a receiver. The guided electromagneticwaves launched and/or received by the coupling device propagate alongthe transmission medium from a sending device to a receiving devicewithout requiring an electrical return path between the sending deviceand the receiving device. In this circumstance, the transmission mediumacts as a waveguide to support the propagation of the guidedelectromagnetic waves from the sending device to the receiving device.

According to an example embodiment, a surface wave is a type of guidedwave that is guided by a surface of a transmission medium, such as anexterior or outer surface or an interior or inner surface including aninterstitial surface of the transmission medium such as the interstitialarea between wires in a multi-stranded cable, insulated twisted pairwires, or wire bundle, and/or another surface of the transmission mediumthat is adjacent to or exposed to another type of medium havingdifferent properties (e.g., dielectric properties). Indeed, in anexample embodiment, a surface of the transmission medium that guides asurface wave can represent a transitional surface between two differenttypes of media. For example, in the case of a bare wire or uninsulatedwire, the surface of the wire can be the outer or exterior conductivesurface of the bare wire or uninsulated wire that is exposed to air orfree space. As another example, in the case of insulated wire, thesurface of the wire can be the conductive portion of the wire that meetsan inner surface of the insulator portion of the wire. A surface of thetransmission medium can be any one of an inner surface of an insulatorsurface of a wire or a conductive surface of the wire that is separatedby a gap composed of, for example, air or free space. A surface of atransmission medium can otherwise be any material region of thetransmission medium. For example, the surface of the transmission mediumcan be an inner portion of an insulator disposed on a conductive portionof the wire that meets the insulator portion of the wire. The surfacethat guides an electromagnetic wave can depend upon the relativedifferences in the properties (e.g., dielectric properties) of theinsulator, air, and/or the conductor and further dependent on thefrequency and propagation mode or modes of the guided wave.

According to an example embodiment, the term “about” a wire or othertransmission medium used in conjunction with a guided wave can includefundamental guided wave propagation modes such as a guided wave having acircular or substantially circular field pattern/distribution, asymmetrical electromagnetic field pattern/distribution (e.g., electricfield or magnetic field) or other fundamental mode pattern at leastpartially around a wire or other transmission medium. Unlike Zenneckwaves that propagate along a single planar surface of a planartransmission medium, the guided electromagnetic waves of the subjectdisclosure that are bound to a transmission medium can haveelectromagnetic field patterns that surround or circumscribe, at leastin part, a non-planar surface of the transmission medium withelectromagnetic energy in all directions, or in all but a finite numberof azimuthal null directions characterized by field strengths thatapproach zero field strength for infinitesimally small azimuthal widths.

For example, such non-circular field distributions can be unilateral ormulti-lateral with one or more axial lobes characterized by relativelyhigher field strength and/or one or more nulls directions of zero fieldstrength or substantially zero-field strength or null regionscharacterized by relatively low-field strength, zero-field strengthand/or substantially zero-field strength. Further, the fielddistribution can otherwise vary as a function of azimuthal orientationaround a transmission medium such that one or more angular regionsaround the transmission medium have an electric or magnetic fieldstrength (or combination thereof) that is higher than one or more otherangular regions of azimuthal orientation, according to an exampleembodiment. It will be appreciated that the relative orientations orpositions of the guided wave higher order modes, particularlyasymmetrical modes, can vary as the guided wave travels along the wire.

In addition, when a guided wave propagates “about” a wire or other typeof transmission medium, it can do so according to a guided wavepropagation mode that includes not only the fundamental wave propagationmodes (e.g., zero order modes), but additionally or alternatively,non-fundamental wave propagation modes such as higher-order guided wavemodes (e.g., 1^(st) order modes, 2^(nd) order modes, etc.). Higher-ordermodes include symmetrical modes that have a circular or substantiallycircular electric or magnetic field distribution and/or a symmetricalelectric or magnetic field distribution, or asymmetrical modes and/orother guided (e.g., surface) waves that have non-circular and/orasymmetrical field distributions around the wire or other transmissionmedium. For example, the guided electromagnetic waves of the subjectdisclosure can propagate along a transmission medium from the sendingdevice to the receiving device or along a coupling device via one ormore guided wave modes such as a fundamental transverse magnetic (TM)TM00 mode (or Goubau mode), a fundamental hybrid mode (EH or HE) “EH00”mode or “HE00” mode, a transverse electromagnetic “TEMnm” mode, a totalinternal reflection (TIR) mode or any other mode such as EHnm, HEnm orTMnm, where n and/or m have integer values greater than or equal to 0,and other fundamental, hybrid and non-fundamental wave modes.

As used herein, the term “guided wave mode” refers to a guided wavepropagation mode of a transmission medium, coupling device or othersystem component of a guided wave communication system that propagatesfor non-trivial distances along the length of the transmission medium,coupling device or other system component.

As used herein, the term “millimeter-wave” can refer to electromagneticwaves/signals that fall within the “millimeter-wave frequency band” of30 GHz to 300 GHz. The term “microwave” can refer to electromagneticwaves/signals that fall within a “microwave frequency band” of 300 MHzto 300 GHz. The term “radio frequency” or “RF” can refer toelectromagnetic waves/signals that fall within the “radio frequencyband” of 10 kHz to 1 THz. It is appreciated that wireless signals,electrical signals, and guided electromagnetic waves as described in thesubject disclosure can be configured to operate at any desirablefrequency range, such as, for example, at frequencies within, above orbelow millimeter-wave and/or microwave frequency bands. In particular,when a coupling device or transmission medium includes a conductiveelement, the frequency of the guided electromagnetic waves that arecarried by the coupling device and/or propagate along the transmissionmedium can be below the mean collision frequency of the electrons in theconductive element. Further, the frequency of the guided electromagneticwaves that are carried by the coupling device and/or propagate along thetransmission medium can be a non-optical frequency, e.g., a radiofrequency below the range of optical frequencies that begins at 1 THz.

It is further appreciated that a transmission medium as described in thesubject disclosure can be configured to be opaque or otherwise resistantto (or at least substantially reduce) a propagation of electromagneticwaves operating at optical frequencies (e.g., greater than 1 THz).

As used herein, the term “antenna” can refer to a device that is part ofa transmitting or receiving system to transmit/radiate or receive freespace wireless signals.

In accordance with one or more embodiments, a method of the subjectdisclosure can include generating, by a voltage waveform generator, analternating voltage periodic waveform directed to a winding coupled to amagnetic core of an inductive power supply to regulate an alternatingmagnetic flux in the magnetic core, wherein the magnetic core comprisesa first portion and a second portion, wherein the first portion of themagnetic core is separable from the second portion of the magnetic core,wherein the magnetic core is magnetically coupled to a conductor thatconducts an alternating current that causes a portion of the alternatingmagnetic flux, wherein the alternating magnetic flux causes a couplingforce between the first portion of the magnetic core and the secondportion of the magnetic core, and wherein the alternating voltageperiodic waveform is generated by selectively enabling one or moreswitches coupled to a storage device, detecting a signal to reduce thecoupling force between the first portion of the magnetic core and thesecond portion of the magnetic core, and responsive to the signal,modifying the regulation of the alternating magnetic flux to reduce thecoupling force between the first portion of the magnetic core and thesecond portion of the magnetic core.

It will be clear to those skilled in the art, after reading the subjectdisclosure, that the coupling force mentioned in the previous paragraphcan be an attractive magnetic force similar to the familiar magneticforce that attracts iron to a magnet. Furthermore, it will also be clearthat such attractive force might make it more difficult to separate thefirst portion of the magnetic core from the second portion in situationswhere such separation is desired.

In accordance with one or more embodiments, an inductive power supply ofthe subject disclosure can include a magnetic core that facilitatescoupling to a conductor that conducts a signal, a winding wrapped arounda cavity of the magnetic core, a storage device, one or more switchescoupled to the winding and the storage device, a processor, and a memorythat stores executable instructions that, when executed by theprocessor, facilitate performance of operations. The operations caninclude generating, by selectively enabling the one or more switchescoupled to the storage device, an alternating voltage periodic waveformdirected to a winding coupled to the magnetic core to regulate analternating magnetic flux in the magnetic core, wherein the magneticcore comprises a first portion and a second portion, wherein the firstportion of the magnetic core is separable from the second portion of themagnetic core, wherein the magnetic core is magnetically coupled to aconductor that conducts an alternating current that causes a portion ofthe alternating magnetic flux, and wherein regulation of the alternatingmagnetic flux causes a coupling force between the first portion of themagnetic core and the second portion of the magnetic core, receiving asignal to reduce the coupling force between the first portion of themagnetic core and the second portion of the magnetic core, andresponsive to the signal, modifying the regulation of the alternatingmagnetic flux to reduce the coupling force between the first portion ofthe magnetic core and the second portion of the magnetic core.

In accordance with one or more embodiments, a method of the subjectdisclosure can include generating an alternating voltage periodicwaveform directed to a winding coupled to a magnetic core of aninductive power supply to regulate an alternating magnetic flux in themagnetic core, wherein the magnetic core comprises a first portion and asecond portion, wherein the first portion of the magnetic core isseparable from the second portion of the magnetic core, wherein themagnetic core is magnetically coupled to a conductor that conducts analternating current that causes a portion of the alternating magneticflux, wherein regulation of the alternating magnetic flux causes acoupling force between the first portion of the magnetic core and thesecond portion of the magnetic core, and responsive to detecting asignal, modifying the regulation of the alternating magnetic flux toreduce the coupling force between the first portion of the magnetic coreand the second portion of the magnetic core.

Referring now to FIG. 1, a block diagram 100 illustrating an example,non-limiting embodiment of a guided wave communications system is shown.In operation, a transmission device 101 receives one or morecommunication signals 110 from a communication network or othercommunications device that includes data and generates guided waves 120to convey the data via the transmission medium 125 to the transmissiondevice 102. The transmission device 102 receives the guided waves 120and converts them to communication signals 112 that include the data fortransmission to a communications network or other communications device.The guided waves 120 can be modulated to convey data via a modulationtechnique such as phase shift keying, frequency shift keying, quadratureamplitude modulation, amplitude modulation, multi-carrier modulationsuch as orthogonal frequency division multiplexing and via multipleaccess techniques such as frequency division multiplexing, time divisionmultiplexing, code division multiplexing, multiplexing via differingwave propagation modes and via other modulation and access strategies.

The communication network or networks can include a wirelesscommunication network such as a mobile data network, a cellular voiceand data network, a wireless local area network (e.g., WiFi or an IEEE802.xx network), a satellite communications network, a personal areanetwork or other wireless network. The communication network or networkscan also include a wired communication network such as a telephonenetwork, an Ethernet network, a local area network, a wide area networksuch as the Internet, a broadband access network, a cable network, afiber optic network, or other wired network. The communication devicescan include a network edge device, bridge device or home gateway, aset-top box, broadband modem, telephone adapter, access point, basestation, or other fixed communication device, a mobile communicationdevice such as an automotive gateway or automobile, laptop computer,tablet, smartphone, cellular telephone, or other communication device.

In an example embodiment, the guided wave communication system 100 canoperate in a bi-directional fashion where transmission device 102receives one or more communication signals 112 from a communicationnetwork or device that includes other data and generates guided waves122 to convey the other data via the transmission medium 125 to thetransmission device 101. In this mode of operation, the transmissiondevice 101 receives the guided waves 122 and converts them tocommunication signals 110 that include the other data for transmissionto a communications network or device. The guided waves 122 can bemodulated to convey data via a modulation technique such as phase shiftkeying, frequency shift keying, quadrature amplitude modulation,amplitude modulation, multi-carrier modulation such as orthogonalfrequency division multiplexing and via multiple access techniques suchas frequency division multiplexing, time division multiplexing, codedivision multiplexing, multiplexing via differing wave propagation modesand via other modulation and access strategies.

The transmission medium 125 can include a cable having at least oneinner portion surrounded by a dielectric material such as an insulatoror other dielectric cover, coating or other dielectric material, thedielectric material having an outer surface and a correspondingcircumference. In an example embodiment, the transmission medium 125operates as a single-wire transmission line to guide the transmission ofan electromagnetic wave. When the transmission medium 125 is implementedas a single wire transmission system, it can include a wire. The wirecan be insulated or uninsulated, and single-stranded or multi-stranded(e.g., braided). In other embodiments, the transmission medium 125 cancontain conductors of other shapes or configurations including wirebundles, cables, rods, rails, pipes. In addition, the transmissionmedium 125 can include non-conductors such as dielectric pipes, rods,rails, or other dielectric members; combinations of conductors anddielectric materials, conductors without dielectric materials or otherguided wave transmission media and/or consist essentially ofnon-conductors such as dielectric pipes, rods, rails, or otherdielectric members that operate without a continuous conductor such asan inner conductor or a conductive shield. It should be noted that thetransmission medium 125 can otherwise include any of the transmissionmedia previously discussed.

Further, as previously discussed, the guided waves 120 and 122 can becontrasted with radio transmissions over free space/air or conventionalpropagation of electrical power or signals through the conductor of awire via an electrical circuit. In addition to the propagation of guidedwaves 120 and 122, the transmission medium 125 may optionally containone or more wires that propagate electrical power or other communicationsignals in a conventional manner as a part of one or more electricalcircuits.

Referring now to FIG. 2, a block diagram 200 illustrating an example,non-limiting embodiment of a transmission device is shown. Thetransmission device 101 or 102 includes a communications interface (I/F)205, a transceiver 210 and a coupler 220.

In an example of operation, the communications interface 205 receives acommunication signal 110 or 112 that includes data. In variousembodiments, the communications interface 205 can include a wirelessinterface for receiving a wireless communication signal in accordancewith a wireless standard protocol such as LTE or other cellular voiceand data protocol, WiFi or an 802.11 protocol, WIMAX protocol, UltraWideband protocol, Bluetooth® protocol, Zigbee® protocol, a directbroadcast satellite (DBS) or other satellite communication protocol orother wireless protocol. In addition or in the alternative, thecommunications interface 205 includes a wired interface that operates inaccordance with an Ethernet protocol, universal serial bus (USB)protocol, a data over cable service interface specification (DOCSIS)protocol, a digital subscriber line (DSL) protocol, a Firewire (IEEE1394) protocol, or other wired protocol. In additional tostandards-based protocols, the communications interface 205 can operatein conjunction with other wired or wireless protocol. In addition, thecommunications interface 205 can optionally operate in conjunction witha protocol stack that includes multiple protocol layers including a MACprotocol, transport protocol, application protocol, etc.

In an example of operation, the transceiver 210 generates anelectromagnetic wave based on the communication signal 110 or 112 toconvey the data. The electromagnetic wave has at least one carrierfrequency and at least one corresponding wavelength. The carrierfrequency can be within a millimeter-wave frequency band of 30 GHz-300GHz, such as 60 GHz or a carrier frequency in the range of 30-40 GHz ora lower frequency band of 300 MHz-30 GHz in the microwave frequencyrange such as 26-30 GHz, 11 GHz, or 3-6 GHz, but it will be appreciatedthat other carrier frequencies are possible in other embodiments. In onemode of operation, the transceiver 210 merely upconverts thecommunications signal or signals 110 or 112 for transmission of theelectromagnetic signal in the microwave or millimeter-wave band as aguided electromagnetic wave that is guided by or bound to thetransmission medium 125. In another mode of operation, thecommunications interface 205 either converts the communication signal110 or 112 to a baseband or near baseband signal or extracts the datafrom the communication signal 110 or 112 and the transceiver 210modulates a high-frequency carrier with the data, the baseband or nearbaseband signal for transmission. It should be appreciated that thetransceiver 210 can modulate the data received via the communicationsignal 110 or 112 to preserve one or more data communication protocolsof the communication signal 110 or 112 either by encapsulation in thepayload of a different protocol or by simple frequency shifting. In thealternative, the transceiver 210 can otherwise translate the datareceived via the communication signal 110 or 112 to a protocol that isdifferent from the data communication protocol or protocols of thecommunication signal 110 or 112.

In an example of operation, the coupler 220 couples the electromagneticwave to the transmission medium 125 as a guided electromagnetic wave toconvey the communications signal or signals 110 or 112. While the priordescription has focused on the operation of the transceiver 210 as atransmitter, the transceiver 210 can also operate to receiveelectromagnetic waves that convey other data from the single wiretransmission medium via the coupler 220 and to generate communicationssignals 110 or 112, via communications interface 205 that includes theother data. Consider embodiments where an additional guidedelectromagnetic wave conveys other data that also propagates along thetransmission medium 125. The coupler 220 can also couple this additionalelectromagnetic wave from the transmission medium 125 to the transceiver210 for reception.

The transmission device 101 or 102 includes an optional trainingcontroller 230. In an example embodiment, the training controller 230 isimplemented by a standalone processor or a processor that is shared withone or more other components of the transmission device 101 or 102. Thetraining controller 230 selects the carrier frequencies, modulationschemes and/or guided wave modes for the guided electromagnetic wavesbased on testing of the transmission medium 125, environmentalconditions and/or feedback data received by the transceiver 210 from atleast one remote transmission device coupled to receive the guidedelectromagnetic wave.

In an example embodiment, a guided electromagnetic wave transmitted by aremote transmission device 101 or 102 conveys data that also propagatesalong the transmission medium 125. The data from the remote transmissiondevice 101 or 102 can be generated to include the feedback data. Inoperation, the coupler 220 also couples the guided electromagnetic wavefrom the transmission medium 125 and the transceiver receives theelectromagnetic wave and processes the electromagnetic wave to extractthe feedback data.

In an example embodiment, the training controller 230 operates based onthe feedback data to evaluate a plurality of candidate frequencies,modulation schemes and/or transmission modes to select a carrierfrequency, modulation scheme and/or transmission mode to enhanceperformance, such as throughput, signal strength, reduce propagationloss, etc.

Consider the following example: a transmission device 101 beginsoperation under control of the training controller 230 by sending aplurality of guided waves as test signals such as pilot waves or othertest signals at a corresponding plurality of candidate frequenciesand/or candidate modes directed to a remote transmission device 102coupled to the transmission medium 125. The guided waves can include, inaddition or in the alternative, test data. The test data can indicatethe particular candidate frequency and/or guide-wave mode of the signal.In an embodiment, the training controller 230 at the remote transmissiondevice 102 receives the test signals and/or test data from any of theguided waves that were properly received and determines the bestcandidate frequency and/or guided wave mode, a set of acceptablecandidate frequencies and/or guided wave modes, or a rank ordering ofcandidate frequencies and/or guided wave modes. This selection ofcandidate frequenc(ies) or/and guided-mode(s) are generated by thetraining controller 230 based on one or more optimizing criteria such asreceived signal strength, bit error rate, packet error rate, signal tonoise ratio, propagation loss, etc. The training controller 230generates feedback data that indicates the selection of candidatefrequenc(ies) or/and guided wave mode(s) and sends the feedback data tothe transceiver 210 for transmission to the transmission device 101. Thetransmission device 101 and 102 can then communicate data with oneanother based on the selection of candidate frequenc(ies) or/and guidedwave mode(s).

In other embodiments, the guided electromagnetic waves that contain thetest signals and/or test data are reflected back, repeated back orotherwise looped back by the remote transmission device 102 to thetransmission device 101 for reception and analysis by the trainingcontroller 230 of the transmission device 101 that initiated thesewaves. For example, the transmission device 101 can send a signal to theremote transmission device 102 to initiate a test mode where a physicalreflector is switched on the line, a termination impedance is changed tocause reflections, a loop back mode is switched on to coupleelectromagnetic waves back to the source transmission device 102, and/ora repeater mode is enabled to amplify and retransmit the electromagneticwaves back to the source transmission device 102. The trainingcontroller 230 at the source transmission device 102 receives the testsignals and/or test data from any of the guided waves that were properlyreceived and determines selection of candidate frequenc(ies) or/andguided wave mode(s).

While the procedure above has been described in a start-up orinitialization mode of operation, each transmission device 101 or 102can send test signals, evaluate candidate frequencies or guided wavemodes via non-test conditions such as normal transmissions or otherwiseevaluate candidate frequencies or guided wave modes at other times orcontinuously as well. In an example embodiment, the communicationprotocol between the transmission devices 101 and 102 can include anon-request or periodic test mode where either full testing or morelimited testing of a subset of candidate frequencies and guided wavemodes are tested and evaluated. In other modes of operation, there-entry into such a test mode can be triggered by a degradation ofperformance due to a disturbance, weather conditions, etc. In an exampleembodiment, the receiver bandwidth of the transceiver 210 is eithersufficiently wide or swept to receive all candidate frequencies or canbe selectively adjusted by the training controller 230 to a trainingmode where the receiver bandwidth of the transceiver 210 is sufficientlywide or swept to receive all candidate frequencies.

Referring now to FIG. 3, a graphical diagram 300 illustrating anexample, non-limiting embodiment of an electromagnetic fielddistribution is shown. In this embodiment, a transmission medium 125 inair includes an inner conductor 301 and an insulating jacket 302 ofdielectric material, as shown in cross section. The diagram 300 includesdifferent gray-scales that represent differing electromagnetic fieldstrengths generated by the propagation of the guided wave having anon-circular and non-fundamental guided wave mode.

In particular, the electromagnetic field distribution corresponds to amodal “sweet spot” that enhances guided electromagnetic wave propagationalong an insulated transmission medium and reduces end-to-endtransmission loss. In this particular mode, electromagnetic waves areguided by the transmission medium 125 to propagate along an outersurface of the transmission medium—in this case, the outer surface ofthe insulating jacket 302. Electromagnetic waves are partially embeddedin the insulator and partially radiating on the outer surface of theinsulator. In this fashion, electromagnetic waves are “lightly” coupledto the insulator so as to enable electromagnetic wave propagation atlong distances with low propagation loss.

As shown, the guided wave has a field structure that lies primarily orsubstantially outside of the transmission medium 125 that serves toguide the electromagnetic waves. The regions inside the conductor 301have little or no field. Likewise regions inside the insulating jacket302 have low field strength. The majority of the electromagnetic fieldstrength is distributed in the lobes 304 at the outer surface of theinsulating jacket 302 and in close proximity thereof. The presence of anon-circular and non-fundamental guided wave mode is shown by the highelectromagnetic field strengths at the top and bottom of the outersurface of the insulating jacket 302 (in the orientation of thediagram)—as opposed to very small field strengths on the other sides ofthe insulating jacket 302.

The example shown corresponds to a 38 GHz electromagnetic wave guided bya wire with a diameter of 1.1 cm and a dielectric insulation ofthickness of 0.36 cm. Because the electromagnetic wave is guided by thetransmission medium 125 and the majority of the field strength isconcentrated in the air outside of the insulating jacket 302 within alimited distance of the outer surface, the guided wave can propagatelongitudinally down the transmission medium 125 with very low loss. Inthe example shown, this “limited distance” corresponds to a distancefrom the outer surface that is less than half the largest crosssectional dimension of the transmission medium 125. In this case, thelargest cross sectional dimension of the wire corresponds to the overalldiameter of 1.82 cm, however, this value can vary with the size andshape of the transmission medium 125. For example, should thetransmission medium 125 be of a rectangular shape with a height of 0.3cm and a width of 0.4 cm, the largest cross sectional dimension would bethe diagonal of 0.5 cm and the corresponding limited distance would be0.25 cm. The dimensions of the area containing the majority of the fieldstrength also vary with the frequency, and in general, increase ascarrier frequencies decrease.

It should also be noted that the components of a guided wavecommunication system, such as couplers and transmission media can havetheir own cut-off frequencies for each guided wave mode. The cut-offfrequency generally sets forth the lowest frequency that a particularguided wave mode is designed to be supported by that particularcomponent. In an example embodiment, the particular non-circular andnon-fundamental mode of propagation shown is induced on the transmissionmedium 125 by an electromagnetic wave having a frequency that fallswithin a limited range (such as Fc to 2Fc) of the cut-off frequency Fcfor this particular non-fundamental mode. The cut-off frequency Fc isparticular to the characteristics of transmission medium 125. Forembodiments as shown that include an inner conductor 301 surrounded byan insulating jacket 302, this cutoff frequency can vary based on thedimensions and properties of the insulating jacket 302 and potentiallythe dimensions and properties of the inner conductor 301 and can bedetermined experimentally to have a desired mode pattern. It should benoted however, that similar effects can be found for a hollow dielectricor insulator without an inner conductor or conductive shield. In thiscase, the cutoff frequency can vary based on the dimensions andproperties of the hollow dielectric or insulator.

At frequencies lower than the cut-off frequency, the non-circular modeis difficult to induce in the transmission medium 125 and fails topropagate for all but trivial distances. As the frequency increasesabove the limited range of frequencies about the cut-off frequency, thenon-circular mode shifts more and more inward of the insulating jacket302. At frequencies much larger than the cut-off frequency, the fieldstrength is no longer concentrated outside of the insulating jacket, butprimarily inside of the insulating jacket 302. While the transmissionmedium 125 provides strong guidance to the electromagnetic wave andpropagation is still possible, ranges are more limited by increasedlosses due to propagation within the insulating jacket 302—as opposed tothe surrounding air.

Referring now to FIG. 4, a graphical diagram 400 illustrating anexample, non-limiting embodiment of an electromagnetic fielddistribution is shown. In particular, a cross section diagram 400,similar to FIG. 3 is shown with common reference numerals used to referto similar elements. The example shown corresponds to a 60 GHz waveguided by a wire with a diameter of 1.1 cm and a dielectric insulationof thickness of 0.36 cm. Because the frequency of the guided wave isabove the limited range of the cut-off frequency of this particularnon-fundamental mode, much of the field strength has shifted inward ofthe insulating jacket 302. In particular, the field strength isconcentrated primarily inside of the insulating jacket 302. While thetransmission medium 125 provides strong guidance to the electromagneticwave and propagation is still possible, ranges are more limited whencompared with the embodiment of FIG. 3, by increased losses due topropagation within the insulating jacket 302.

Referring now to FIG. 5A, a graphical diagram illustrating an example,non-limiting embodiment of a frequency response is shown. In particular,diagram 500 presents a graph of end-to-end loss (in dB) as a function offrequency, overlaid with electromagnetic field distributions 510, 520and 530 at three points for a 200 cm insulated medium voltage wire. Theboundary between the insulator and the surrounding air is represented byreference numeral 525 in each electromagnetic field distribution.

As discussed in conjunction with FIG. 3, an example of a desirednon-circular mode of propagation shown is induced on the transmissionmedium 125 by an electromagnetic wave having a frequency that fallswithin a limited range (such as Fc to 2Fc) of the lower cut-offfrequency Fc of the transmission medium for this particular non-circularmode. In particular, the electromagnetic field distribution 520 at 6 GHzfalls within this modal “sweet spot” that enhances electromagnetic wavepropagation along an insulated transmission medium and reducesend-to-end transmission loss. In this particular mode, guided waves arepartially embedded in the insulator and partially radiating on the outersurface of the insulator. In this fashion, the electromagnetic waves are“lightly” coupled to the insulator so as to enable guidedelectromagnetic wave propagation at long distances with low propagationloss.

At lower frequencies represented by the electromagnetic fielddistribution 510 at 3 GHz, the non-circular mode radiates more heavilygenerating higher propagation losses. At higher frequencies representedby the electromagnetic field distribution 530 at 9 GHz, the non-circularmode shifts more and more inward of the insulating jacket providing toomuch absorption, again generating higher propagation losses.

Referring now to FIG. 5B, a graphical diagram 550 illustrating example,non-limiting embodiments of a longitudinal cross-section of atransmission medium 125, such as an insulated wire, depicting fields ofguided electromagnetic waves at various operating frequencies is shown.As shown in diagram 556, when the guided electromagnetic waves are atapproximately the cutoff frequency (f_(c)) corresponding to the modal“sweet spot”, the guided electromagnetic waves are loosely coupled tothe insulated wire so that absorption is reduced, and the fields of theguided electromagnetic waves are bound sufficiently to reduce the amountradiated into the environment (e.g., air). Because absorption andradiation of the fields of the guided electromagnetic waves is low,propagation losses are consequently low, enabling the guidedelectromagnetic waves to propagate for longer distances.

As shown in diagram 554, propagation losses increase when an operatingfrequency of the guide electromagnetic waves increases above abouttwo-times the cutoff frequency (f_(c))—or as referred to, above therange of the “sweet spot”. More of the field strength of theelectromagnetic wave is driven inside the insulating layer, increasingpropagation losses. At frequencies much higher than the cutoff frequency(f_(c)) the guided electromagnetic waves are strongly bound to theinsulated wire as a result of the fields emitted by the guidedelectromagnetic waves being concentrated in the insulation layer of thewire, as shown in diagram 552. This in turn raises propagation lossesfurther due to absorption of the guided electromagnetic waves by theinsulation layer. Similarly, propagation losses increase when theoperating frequency of the guided electromagnetic waves is substantiallybelow the cutoff frequency (f_(c)), as shown in diagram 558. Atfrequencies much lower than the cutoff frequency (f_(c)) the guidedelectromagnetic waves are weakly (or nominally) bound to the insulatedwire and thereby tend to radiate into the environment (e.g., air), whichin turn, raises propagation losses due to radiation of the guidedelectromagnetic waves.

Referring now to FIG. 6, a graphical diagram 600 illustrating anexample, non-limiting embodiment of an electromagnetic fielddistribution is shown. In this embodiment, a transmission medium 602 isa bare wire, as shown in cross section. The diagram 600 includesdifferent gray-scales that represent differing electromagnetic fieldstrengths generated by the propagation of a guided wave having asymmetrical and fundamental TM00 guided wave mode at a single carrierfrequency.

In this particular mode, electromagnetic waves are guided by thetransmission medium 602 to propagate along an outer surface of thetransmission medium—in this case, the outer surface of the bare wire.Electromagnetic waves are “lightly” coupled to the wire so as to enableelectromagnetic wave propagation at long distances with low propagationloss. As shown, the guided wave has a field structure that liessubstantially outside of the transmission medium 602 that serves toguide the electromagnetic waves. The regions inside the conductor of thetransmission medium 602 have little or no field strength.

Referring now to FIG. 7, a block diagram 700 illustrating an example,non-limiting embodiment of an arc coupler is shown. In particular acoupling device is presented for use in a transmission device, such astransmission device 101 or 102 presented in conjunction with FIG. 1. Thecoupling device includes an arc coupler 704 coupled to a transmittercircuit 712 and termination or damper 714. The arc coupler 704 can bemade of a dielectric material, or other low-loss insulator (e.g.,Teflon, polyethylene, etc.), or made of a conducting (e.g., metallic,non-metallic, etc.) material, or any combination of the foregoingmaterials. As shown, the arc coupler 704 operates as a waveguide and hasa wave 706 propagating as a guided wave, within and about a waveguidesurface of the arc coupler 704. In the embodiment shown, at least aportion of the arc coupler 704 can be placed near a wire 702 or othertransmission medium, (such as transmission medium 125), in order tofacilitate coupling between the arc coupler 704 and the wire 702 orother transmission medium, as described herein to launch the guided wave708 on the wire. The arc coupler 704 can be placed such that a portionof the curved arc coupler 704 is tangential to, and parallel orsubstantially parallel to the wire 702. The portion of the arc coupler704 that is parallel to the wire can be an apex of the curve, or anypoint where a tangent of the curve is parallel to the wire 702. When thearc coupler 704 is positioned or placed thusly, the wave 706 travellingalong the arc coupler 704 couples, at least in part, to the wire 702,and propagates as guided wave 708 around or about the wire surface ofthe wire 702 and longitudinally along the wire 702. The guided wave 708can be characterized as a surface wave or other electromagnetic wavethat is guided by or bound to the wire 702 or other transmission medium.

A portion of the wave 706 that does not couple to the wire 702propagates as a wave 710 along the arc coupler 704. It will beappreciated that the arc coupler 704 can be configured and arranged in avariety of positions in relation to the wire 702 to achieve a desiredlevel of coupling or non-coupling of the wave 706 to the wire 702. Forexample, the curvature and/or length of the arc coupler 704 that isparallel or substantially parallel, as well as its separation distance(which can include zero separation distance in an embodiment), to thewire 702 can be varied without departing from example embodiments.Likewise, the arrangement of arc coupler 704 in relation to the wire 702may be varied based upon considerations of the respective intrinsiccharacteristics (e.g., thickness, composition, electromagneticproperties, etc.) of the wire 702 and the arc coupler 704, as well asthe characteristics (e.g., frequency, energy level, etc.) of the waves706 and 708.

The guided wave 708 stays parallel or substantially parallel to the wire702, even as the wire 702 bends and flexes. Bends in the wire 702 canincrease transmission losses, which are also dependent on wirediameters, frequency, and materials. If the dimensions of the arccoupler 704 are chosen for efficient power transfer, most of the powerin the wave 706 is transferred to the wire 702, with little powerremaining in wave 710. It will be appreciated that the guided wave 708can still be multi-modal in nature (discussed herein), including havingmodes that are non-circular, non-fundamental and/or asymmetric, whiletraveling along a path that is parallel or substantially parallel to thewire 702, with or without a fundamental transmission mode. In anembodiment, non-circular, non-fundamental and/or asymmetric modes can beutilized to minimize transmission losses and/or obtain increasedpropagation distances.

It is noted that the term “parallel” is generally a geometric constructwhich often is not exactly achievable in real systems. Accordingly, theterm “parallel” as utilized in the subject disclosure represents anapproximation rather than an exact configuration when used to describeembodiments disclosed in the subject disclosure. In an embodiment,“substantially parallel” can include approximations that are within 30degrees of true parallel in all dimensions.

In an embodiment, the wave 706 can exhibit one or more wave propagationmodes. The arc coupler modes can be dependent on the shape and/or designof the coupler 704. The one or more arc coupler modes of wave 706 cangenerate, influence, or impact one or more wave propagation modes of theguided wave 708 propagating along wire 702. It should be particularlynoted however that the guided wave modes present in the guided wave 706may be the same or different from the guided wave modes of the guidedwave 708. In this fashion, one or more guided wave modes of the guidedwave 706 may not be transferred to the guided wave 708, and further oneor more guided wave modes of guided wave 708 may not have been presentin guided wave 706. It should also be noted that the cut-off frequencyof the arc coupler 704 for a particular guided wave mode may bedifferent than the cutoff frequency of the wire 702 or othertransmission medium for that same mode. For example, while the wire 702or other transmission medium may be operated slightly above its cutofffrequency for a particular guided wave mode, the arc coupler 704 may beoperated well above its cut-off frequency for that same mode for lowloss, slightly below its cut-off frequency for that same mode to, forexample, induce greater coupling and power transfer, or some other pointin relation to the arc coupler's cutoff frequency for that mode.

In an embodiment, the wave propagation modes on the wire 702 can besimilar to the arc coupler modes since both waves 706 and 708 propagateabout the outside of the arc coupler 704 and wire 702 respectively. Insome embodiments, as the wave 706 couples to the wire 702, the modes canchange form, or new modes can be created or generated, due to thecoupling between the arc coupler 704 and the wire 702. For example,differences in size, material, and/or impedances of the arc coupler 704and wire 702 may create additional modes not present in the arc couplermodes and/or suppress some of the arc coupler modes. The wavepropagation modes can comprise the fundamental transverse magnetic mode(TM₀₀), where only small magnetic fields extend in the direction ofpropagation, and the electric field extends radially outwards and thenlongitudinally while the guided wave propagates along the wire. Thisguided wave mode can be donut shaped, where only a portion of theelectromagnetic fields exist within the arc coupler 704 or wire 702.

While the waves 706 and 708 can comprise a fundamental TM mode, thewaves 706 and 708, also or in the alternative, can comprisenon-fundamental TM modes. While particular wave propagation modes arediscussed above, other wave propagation modes in or along the couplerand/or along the wire are likewise possible such as transverse electric(TE) and hybrid (EH or HE) modes, based on the frequencies employed, thedesign of the arc coupler 704, the dimensions and composition of thewire 702, as well as its surface characteristics, its insulation ifpresent, the electromagnetic properties of the surrounding environment,etc. It should be noted that, depending on the frequency, the electricaland physical characteristics of the wire 702 and the particular wavepropagation modes that are generated, guided wave 708 can travel alongthe conductive surface of an oxidized uninsulated wire, an unoxidizeduninsulated wire, an insulated wire and/or along the insulating surfaceof an insulated wire.

In an embodiment, a diameter of the arc coupler 704 is smaller than thediameter of the wire 702. For the millimeter-band wavelength being used,the arc coupler 704 supports a single waveguide mode that makes up wave706. This single waveguide mode can change as it couples to the wire 702as guided wave 708. If the arc coupler 704 were larger, more than onewaveguide mode can be supported, but these additional waveguide modesmay not couple to the wire 702 as efficiently, and higher couplinglosses can result. However, in some alternative embodiments, thediameter of the arc coupler 704 can be equal to or larger than thediameter of the wire 702, for example, where higher coupling losses aredesirable or when used in conjunction with other techniques to otherwisereduce coupling losses (e.g., impedance matching with tapering, etc.).

In an embodiment, the wavelength of the waves 706 and 708 are comparablein size, or smaller than a circumference of the arc coupler 704 and thewire 702. In an example, if the wire 702 has a diameter of 0.5 cm, and acorresponding circumference of around 1.5 cm, the wavelength of thetransmission is around 1.5 cm or less, corresponding to a frequency of70 GHz or greater. In another embodiment, a suitable frequency of thetransmission and the carrier-wave signal is in the range of 30-100 GHz,perhaps around 30-60 GHz, and around 38 GHz in one example. In anembodiment, when the circumference of the arc coupler 704 and wire 702is comparable in size to, or greater, than a wavelength of thetransmission, the waves 706 and 708 can exhibit multiple wavepropagation modes including fundamental and/or non-fundamental(symmetric and/or asymmetric, circular and/or non-circular) modes thatpropagate over sufficient distances to support various communicationsystems described herein. The waves 706 and 708 can therefore comprisemore than one type of electric and magnetic field configuration. In anembodiment, as the guided wave 708 propagates down the wire 702, theelectrical and magnetic field configurations will remain the same fromend to end of the wire 702. In other embodiments, as the guided wave 708encounters interference (distortion or obstructions) or loses energy dueto transmission losses or scattering, the electric and magnetic fieldconfigurations can change as the guided wave 708 propagates down wire702.

In an embodiment, the arc coupler 704 can be composed of nylon, Teflon,polyethylene, a polyamide, or other plastics. In other embodiments,other dielectric materials can be employed. The wire surface of wire 702can be metallic with either a bare metallic surface, or can be insulatedusing plastic, dielectric, insulator or other coating, jacket orsheathing. In an embodiment, a dielectric or otherwisenon-conducting/insulated waveguide can be paired with either abare/metallic wire or insulated wire. In other embodiments, a metallicand/or conductive waveguide can be paired with a bare/metallic wire orinsulated wire. In an embodiment, an oxidation layer on the baremetallic surface of the wire 702 (e.g., resulting from exposure of thebare metallic surface to oxygen/air) can also provide insulating ordielectric properties similar to those provided by some insulators orsheathings.

It is noted that the graphical representations of waves 706, 708 and 710are presented merely to illustrate the principles that wave 706 inducesor otherwise launches a guided wave 708 on a wire 702 that operates, forexample, as a single wire transmission line. Wave 710 represents theportion of wave 706 that remains on the arc coupler 704 after thegeneration of guided wave 708. The actual electric and magnetic fieldsgenerated as a result of such wave propagation may vary depending on thefrequencies employed, the particular wave propagation mode or modes, thedesign of the arc coupler 704, the dimensions and composition of thewire 702, as well as its surface characteristics, its optionalinsulation, the electromagnetic properties of the surroundingenvironment, etc.

It is noted that arc coupler 704 can include a termination circuit ordamper 714 at the end of the arc coupler 704 that can absorb leftoverradiation or energy from wave 710. The termination circuit or damper 714can prevent and/or minimize the leftover radiation or energy from wave710 reflecting back toward transmitter circuit 712. In an embodiment,the termination circuit or damper 714 can include termination resistors,absorbing materials and/or other components that perform impedancematching to attenuate reflection. In some embodiments, if the couplingefficiencies are high enough, and/or wave 710 is sufficiently small, itmay not be necessary to use a termination circuit or damper 714. For thesake of simplicity, these transmitter 712 and termination circuits ordampers 714 may not be depicted in the other figures, but in thoseembodiments, transmitter and termination circuits or dampers maypossibly be used.

Further, while a single arc coupler 704 is presented that generates asingle guided wave 708, multiple arc couplers 704 placed at differentpoints along the wire 702 and/or at different azimuthal orientationsabout the wire can be employed to generate and receive multiple guidedwaves 708 at the same or different frequencies, at the same or differentphases, at the same or different wave propagation modes.

FIG. 8, a block diagram 800 illustrating an example, non-limitingembodiment of an arc coupler is shown. In the embodiment shown, at leasta portion of the coupler 704 can be placed near a wire 702 or othertransmission medium, (such as transmission medium 125), in order tofacilitate coupling between the arc coupler 704 and the wire 702 orother transmission medium, to extract a portion of the guided wave 806as a guided wave 808 as described herein. The arc coupler 704 can beplaced such that a portion of the curved arc coupler 704 is tangentialto, and parallel or substantially parallel to the wire 702. The portionof the arc coupler 704 that is parallel to the wire can be an apex ofthe curve, or any point where a tangent of the curve is parallel to thewire 702. When the arc coupler 704 is positioned or placed thusly, thewave 806 travelling along the wire 702 couples, at least in part, to thearc coupler 704, and propagates as guided wave 808 along the arc coupler704 to a receiving device (not expressly shown). A portion of the wave806 that does not couple to the arc coupler propagates as wave 810 alongthe wire 702 or other transmission medium.

In an embodiment, the wave 806 can exhibit one or more wave propagationmodes. The arc coupler modes can be dependent on the shape and/or designof the coupler 704. The one or more modes of guided wave 806 cangenerate, influence, or impact one or more guide-wave modes of theguided wave 808 propagating along the arc coupler 704. It should beparticularly noted however that the guided wave modes present in theguided wave 806 may be the same or different from the guided wave modesof the guided wave 808. In this fashion, one or more guided wave modesof the guided wave 806 may not be transferred to the guided wave 808,and further one or more guided wave modes of guided wave 808 may nothave been present in guided wave 806.

Referring now to FIG. 9A, a block diagram 900 illustrating an example,non-limiting embodiment of a stub coupler is shown. In particular acoupling device that includes stub coupler 904 is presented for use in atransmission device, such as transmission device 101 or 102 presented inconjunction with FIG. 1. The stub coupler 904 can be made of adielectric material, or other low-loss insulator (e.g., Teflon,polyethylene and etc.), or made of a conducting (e.g., metallic,non-metallic, etc.) material, or any combination of the foregoingmaterials. As shown, the stub coupler 904 operates as a waveguide andhas a wave 906 propagating as a guided wave within and about a waveguidesurface of the stub coupler 904. In the embodiment shown, at least aportion of the stub coupler 904 can be placed near a wire 702 or othertransmission medium, (such as transmission medium 125), in order tofacilitate coupling between the stub coupler 904 and the wire 702 orother transmission medium, as described herein to launch the guided wave908 on the wire.

In an embodiment, the stub coupler 904 is curved, and an end of the stubcoupler 904 can be tied, fastened, or otherwise mechanically coupled toa wire 702. When the end of the stub coupler 904 is fastened to the wire702, the end of the stub coupler 904 is parallel or substantiallyparallel to the wire 702. Alternatively, another portion of thedielectric waveguide beyond an end can be fastened or coupled to wire702 such that the fastened or coupled portion is parallel orsubstantially parallel to the wire 702. The fastener 910 can be a nyloncable tie or other type of non-conducting/dielectric material that iseither separate from the stub coupler 904 or constructed as anintegrated component of the stub coupler 904. The stub coupler 904 canbe adjacent to the wire 702 without surrounding the wire 702.

Like the arc coupler 704 described in conjunction with FIG. 7, when thestub coupler 904 is placed with the end parallel to the wire 702, theguided wave 906 travelling along the stub coupler 904 couples to thewire 702, and propagates as guided wave 908 about the wire surface ofthe wire 702. In an example embodiment, the guided wave 908 can becharacterized as a surface wave or other electromagnetic wave.

It is noted that the graphical representations of waves 906 and 908 arepresented merely to illustrate the principles that wave 906 induces orotherwise launches a guided wave 908 on a wire 702 that operates, forexample, as a single wire transmission line. The actual electric andmagnetic fields generated as a result of such wave propagation may varydepending on one or more of the shape and/or design of the coupler, therelative position of the dielectric waveguide to the wire, thefrequencies employed, the design of the stub coupler 904, the dimensionsand composition of the wire 702, as well as its surface characteristics,its optional insulation, the electromagnetic properties of thesurrounding environment, etc.

In an embodiment, an end of stub coupler 904 can taper towards the wire702 in order to increase coupling efficiencies. Indeed, the tapering ofthe end of the stub coupler 904 can provide impedance matching to thewire 702 and reduce reflections, according to an example embodiment ofthe subject disclosure. For example, an end of the stub coupler 904 canbe gradually tapered in order to obtain a desired level of couplingbetween waves 906 and 908 as illustrated in FIG. 9A.

In an embodiment, the fastener 910 can be placed such that there is ashort length of the stub coupler 904 between the fastener 910 and an endof the stub coupler 904. Maximum coupling efficiencies are realized inthis embodiment when the length of the end of the stub coupler 904 thatis beyond the fastener 910 is at least several wavelengths long forwhatever frequency is being transmitted.

Turning now to FIG. 9B, a diagram 950 illustrating an example,non-limiting embodiment of an electromagnetic distribution in accordancewith various aspects described herein is shown. In particular, anelectromagnetic distribution is presented in two dimensions for atransmission device that includes coupler 952, shown in an example stubcoupler constructed of a dielectric material. The coupler 952 couples anelectromagnetic wave for propagation as a guided wave along an outersurface of a wire 702 or other transmission medium.

The coupler 952 guides the electromagnetic wave to a junction at x₀ viaa symmetrical guided wave mode. While some of the energy of theelectromagnetic wave that propagates along the coupler 952 is outside ofthe coupler 952, the majority of the energy of this electromagnetic waveis contained within the coupler 952. The junction at x₀ couples theelectromagnetic wave to the wire 702 or other transmission medium at anazimuthal angle corresponding to the bottom of the transmission medium.This coupling induces an electromagnetic wave that is guided topropagate along the outer surface of the wire 702 or other transmissionmedium via at least one guided wave mode in direction 956. The majorityof the energy of the guided electromagnetic wave is outside or, but inclose proximity to the outer surface of the wire 702 or othertransmission medium. In the example shown, the junction at x₀ forms anelectromagnetic wave that propagates via both a fundamental TM00 modeand at least one non-fundamental mode, such as the first order modepresented in conjunction with FIG. 3, that skims the surface of the wire702 or other transmission medium.

It is noted that the graphical representations of guided waves arepresented merely to illustrate an example of guided wave coupling andpropagation. The actual electric and magnetic fields generated as aresult of such wave propagation may vary depending on the frequenciesemployed, the design and/or configuration of the coupler 952, thedimensions and composition of the wire 702 or other transmission medium,as well as its surface characteristics, its insulation if present, theelectromagnetic properties of the surrounding environment, etc.

Turning now to FIG. 10, illustrated is a block diagram 1000 of anexample, non-limiting embodiment of a coupler and transceiver system inaccordance with various aspects described herein. The system is anexample of transmission device 101 or 102. In particular, thecommunications interface 1008 is an example of communications interface205, the stub coupler 1002 is an example of coupler 220, and thetransmitter/receiver device 1006, diplexer 1016, power amplifier 1014,low noise amplifier 1018, frequency mixers 1010 and 1020 and localoscillator 1012 collectively form an example of transceiver 210.

In operation, the transmitter/receiver device 1006 launches and receiveswaves (e.g., guided wave 1004 onto stub coupler 1002). The guided waves1004 can be used to transport signals received from and sent to a hostdevice, base station, mobile devices, a building or other device by wayof a communications interface 1008. The communications interface 1008can be an integral part of system 1000. Alternatively, thecommunications interface 1008 can be tethered to system 1000. Thecommunications interface 1008 can comprise a wireless interface forinterfacing to the host device, base station, mobile devices, a buildingor other device utilizing any of various present or future wirelesssignaling protocols (e.g., LTE, WiFi, WiMAX, IEEE 802.xx, 5G, etc.)including an infrared protocol such as an infrared data association(IrDA) protocol or other line of sight optical protocol. Thecommunications interface 1008 can also comprise a wired interface suchas a fiber optic line, coaxial cable, twisted pair, category 5 (CAT-5)cable or other suitable wired or optical mediums for communicating withthe host device, base station, mobile devices, a building or otherdevice via a protocol such as an Ethernet protocol, universal serial bus(USB) protocol, a data over cable service interface specification(DOCSIS) protocol, a digital subscriber line (DSL) protocol, a Firewire(IEEE 1394) protocol, or other wired or optical protocol. Forembodiments where system 1000 functions as a repeater, thecommunications interface 1008 may not be necessary.

The output signals (e.g., Tx) of the communications interface 1008 canbe combined with a carrier wave (e.g., millimeter-wave carrier wave)generated by a local oscillator 1012 at frequency mixer 1010. Frequencymixer 1010 can use heterodyning techniques or other frequency shiftingtechniques to frequency shift the output signals from communicationsinterface 1008. For example, signals sent to and from the communicationsinterface 1008 can be modulated signals such as orthogonal frequencydivision multiplexed (OFDM) signals formatted in accordance with aLong-Term Evolution (LTE) wireless protocol or other wireless 3G, 4G, 5Gor higher voice and data protocol, a Zigbee®, WIMAX, UltraWideband orIEEE 802.11 wireless protocol; a wired protocol such as an Ethernetprotocol, universal serial bus (USB) protocol, a data over cable serviceinterface specification (DOCSIS) protocol, a digital subscriber line(DSL) protocol, a Firewire (IEEE 1394) protocol or other wired orwireless protocol. In an example embodiment, this frequency conversioncan be done in the analog domain, and as a result, the frequencyshifting can be done without regard to the type of communicationsprotocol used by a base station, mobile devices, or in-building devices.As new communications technologies are developed, the communicationsinterface 1008 can be upgraded (e.g., updated with software, firmware,and/or hardware) or replaced and the frequency shifting and transmissionapparatus can remain, simplifying upgrades. The carrier wave can then besent to a power amplifier (“PA”) 1014 and can be transmitted via thetransmitter receiver device 1006 via the diplexer 1016.

Signals received from the transmitter/receiver device 1006 that aredirected towards the communications interface 1008 can be separated fromother signals via diplexer 1016. The received signal can then be sent tolow noise amplifier (“LNA”) 1018 for amplification. A frequency mixer1020, with help from local oscillator 1012 can downshift the receivedsignal (which is in the millimeter-wave band or around 38 GHz in someembodiments) to the native frequency. The communications interface 1008can then receive the transmission at an input port (Rx).

In an embodiment, transmitter/receiver device 1006 can include acylindrical or non-cylindrical metal (which, for example, can be hollowin an embodiment, but not necessarily drawn to scale) or otherconducting or non-conducting waveguide and an end of the stub coupler1002 can be placed in or in proximity to the waveguide or thetransmitter/receiver device 1006 such that when the transmitter/receiverdevice 1006 generates a transmission, the guided wave couples to stubcoupler 1002 and propagates as a guided wave 1004 about the waveguidesurface of the stub coupler 1002. In some embodiments, the guided wave1004 can propagate in part on the outer surface of the stub coupler 1002and in part inside the stub coupler 1002. In other embodiments, theguided wave 1004 can propagate substantially or completely on the outersurface of the stub coupler 1002. In yet other embodiments, the guidedwave 1004 can propagate substantially or completely inside the stubcoupler 1002. In this latter embodiment, the guided wave 1004 canradiate at an end of the stub coupler 1002 (such as the tapered endshown in FIG. 4) for coupling to a transmission medium such as a wire702 of FIG. 7. Similarly, if guided wave 1004 is incoming (coupled tothe stub coupler 1002 from a wire 702), guided wave 1004 then enters thetransmitter/receiver device 1006 and couples to the cylindricalwaveguide or conducting waveguide. While transmitter/receiver device1006 is shown to include a separate waveguide—an antenna, cavityresonator, klystron, magnetron, travelling wave tube, or other radiatingelement can be employed to induce a guided wave on the coupler 1002,with or without the separate waveguide.

In an embodiment, stub coupler 1002 can be wholly constructed of adielectric material (or another suitable insulating material), withoutany metallic or otherwise conducting materials therein. Stub coupler1002 can be composed of nylon, Teflon, polyethylene, a polyamide, otherplastics, or other materials that are non-conducting and suitable forfacilitating transmission of electromagnetic waves at least in part onan outer surface of such materials. In another embodiment, stub coupler1002 can include a core that is conducting/metallic, and have anexterior dielectric surface. Similarly, a transmission medium thatcouples to the stub coupler 1002 for propagating electromagnetic wavesinduced by the stub coupler 1002 or for supplying electromagnetic wavesto the stub coupler 1002 can, in addition to being a bare or insulatedwire, be wholly constructed of a dielectric material (or anothersuitable insulating material), without any metallic or otherwiseconducting materials therein.

It is noted that although FIG. 10 shows that the opening of transmitterreceiver device 1006 is much wider than the stub coupler 1002, this isnot to scale, and that in other embodiments the width of the stubcoupler 1002 is comparable or slightly smaller than the opening of thehollow waveguide. It is also not shown, but in an embodiment, an end ofthe coupler 1002 that is inserted into the transmitter/receiver device1006 tapers down in order to reduce reflection and increase couplingefficiencies. The stub coupler 1002 can be representative of the archcoupler 704 of FIGS. 7 and 8, the stub coupler 904 of FIG. 9A, thecoupler 952, or any other couplers described in the subject disclosure.

Before coupling to the stub coupler 1002, the one or more waveguidemodes of the guided wave generated by the transmitter/receiver device1006 can couple to the stub coupler 1002 to induce one or more wavepropagation modes of the guided wave 1004. The wave propagation modes ofthe guided wave 1004 can be different than the hollow metal waveguidemodes due to the different characteristics of the hollow metal waveguideand the dielectric waveguide. For instance, wave propagation modes ofthe guided wave 1004 can comprise the fundamental transverse magneticmode (TM₀₀), where only small magnetic fields extend in the direction ofpropagation, HE11 or other modes supported by the stub coupler 1002 thatgenerate one or more desired wave modes on the transmission medium. Thefundamental transverse electromagnetic mode wave propagation mode may ormay not exist inside a waveguide that is hollow. Therefore, the hollowmetal waveguide modes that are used by transmitter/receiver device 1006are waveguide modes, such as TE01 or TE11, that can propagate inside acircular, rectangular or other hollow metallic waveguide and coupleeffectively and efficiently to wave propagation modes of stub coupler1002.

It will be appreciated that other constructs or combinations of thetransmitter/receiver device 1006 and stub coupler 1002 are possible.

Referring now to FIG. 11, a block diagram 1100 illustrating an example,non-limiting embodiment of a dual stub coupler is shown. In particular,a dual coupler design is presented for use in a transmission device,such as transmission device 101 or 102 presented in conjunction withFIG. 1. In an embodiment, two or more couplers (such as the stubcouplers 1104 and 1106) can be positioned around a wire 1102 in order toreceive guided wave 1108. In an embodiment, one coupler is enough toreceive the guided wave 1108. In that case, guided wave 1108 couples tocoupler 1104 and propagates as guided wave 1110. If the field structureof the guided wave 1108 oscillates or undulates around the wire 1102 dueto the particular guided wave mode(s) or various outside factors, thencoupler 1106 can be placed such that guided wave 1108 couples to coupler1106. In some embodiments, four or more couplers can be placed around aportion of the wire 1102, e.g., at 90 degrees or another spacing withrespect to each other, in order to receive guided waves that mayoscillate or rotate around the wire 1102, that have been induced atdifferent azimuthal orientations or that have non-fundamental or higherorder modes that, for example, have lobes and/or nulls or otherasymmetries that are orientation dependent. However, it will beappreciated that there may be less than or more than four couplersplaced around a portion of the wire 1102 without departing from exampleembodiments.

It should be noted that while couplers 1106 and 1104 are illustrated asstub couplers, any other of the coupler designs described hereinincluding arc couplers, antenna or horn couplers, magnetic couplers,etc., could likewise be used. It will also be appreciated that whilesome example embodiments have presented a plurality of couplers aroundat least a portion of a wire 1102, this plurality of couplers can alsobe considered as part of a single coupler system having multiple couplersubcomponents. For example, two or more couplers can be manufactured assingle system that can be installed around a wire in a singleinstallation such that the couplers are either pre-positioned oradjustable relative to each other (either manually or automatically witha controllable mechanism such as a motor or other actuator) inaccordance with the single system.

Receivers coupled to couplers 1106 and 1104 can use diversity combiningto combine signals received from both couplers 1106 and 1104 in order tomaximize the signal quality. In other embodiments, if one or the otherof the couplers 1104 and 1106 receive a transmission that is above apredetermined threshold, receivers can use selection diversity whendeciding which signal to use. Further, while reception by a plurality ofcouplers 1106 and 1104 is illustrated, transmission by couplers 1106 and1104 in the same configuration can likewise take place. In particular, awide range of multi-input multi-output (MIMO) transmission and receptiontechniques can be employed for transmissions where a transmissiondevice, such as transmission device 101 or 102 presented in conjunctionwith FIG. 1 includes multiple transceivers and multiple couplers. Forexample, such MIMO transmission and reception techniques includeprecoding, spatial multiplexing, diversity coding and guided wave modedivision multiplexing applied to transmission and reception by multiplecouplers/launchers that operate on a transmission medium with one ormore surfaces that support guided wave communications.

It is noted that the graphical representations of waves 1108 and 1110are presented merely to illustrate the principles that guided wave 1108induces or otherwise launches a wave 1110 on a coupler 1104. The actualelectric and magnetic fields generated as a result of such wavepropagation may vary depending on the frequencies employed, the designof the coupler 1104, the dimensions and composition of the wire 1102, aswell as its surface characteristics, its insulation if any, theelectromagnetic properties of the surrounding environment, etc.

Referring now to FIG. 12, a block diagram 1200 illustrating an example,non-limiting embodiment of a repeater system is shown. In particular, arepeater device 1210 is presented for use in a transmission device, suchas transmission device 101 or 102 presented in conjunction with FIG. 1.In this system, two couplers 1204 and 1214 can be placed near a wire1202 or other transmission medium such that guided waves 1205propagating along the wire 1202 are extracted by coupler 1204 as wave1206 (e.g. as a guided wave), and then are boosted or repeated byrepeater device 1210 and launched as a wave 1216 (e.g. as a guided wave)onto coupler 1214. The wave 1216 can then be launched on the wire 1202and continue to propagate along the wire 1202 as a guided wave 1217. Inan embodiment, the repeater device 1210 can receive at least a portionof the power utilized for boosting or repeating through magneticcoupling with the wire 1202, for example, when the wire 1202 is a powerline or otherwise contains a power-carrying conductor. It should benoted that while couplers 1204 and 1214 are illustrated as stubcouplers, any other of the coupler designs described herein includingarc couplers, antenna or horn couplers, magnetic couplers, or the like,could likewise be used.

In some embodiments, repeater device 1210 can repeat the transmissionassociated with wave 1206, and in other embodiments, repeater device1210 can include a communications interface 205 that extracts data orother signals from the wave 1206 for supplying such data or signals toanother network and/or one or more other devices as communicationsignals 110 or 112 and/or receiving communication signals 110 or 112from another network and/or one or more other devices and launch guidedwave 1216 having embedded therein the received communication signals 110or 112. In a repeater configuration, receiver waveguide 1208 can receivethe wave 1206 from the coupler 1204 and transmitter waveguide 1212 canlaunch guided wave 1216 onto coupler 1214 as guided wave 1217. Betweenreceiver waveguide 1208 and transmitter waveguide 1212, the signalembedded in guided wave 1206 and/or the guided wave 1216 itself can beamplified to correct for signal loss and other inefficiencies associatedwith guided wave communications or the signal can be received andprocessed to extract the data contained therein and regenerated fortransmission. In an embodiment, the receiver waveguide 1208 can beconfigured to extract data from the signal, process the data to correctfor data errors utilizing for example error correcting codes, andregenerate an updated signal with the corrected data. The transmitterwaveguide 1212 can then transmit guided wave 1216 with the updatedsignal embedded therein. In an embodiment, a signal embedded in guidedwave 1206 can be extracted from the transmission and processed forcommunication with another network and/or one or more other devices viacommunications interface 205 as communication signals 110 or 112.Similarly, communication signals 110 or 112 received by thecommunications interface 205 can be inserted into a transmission ofguided wave 1216 that is generated and launched onto coupler 1214 bytransmitter waveguide 1212.

It is noted that although FIG. 12 shows guided wave transmissions 1206and 1216 entering from the left and exiting to the right respectively,this is merely a simplification and is not intended to be limiting. Inother embodiments, receiver waveguide 1208 and transmitter waveguide1212 can also function as transmitters and receivers respectively,allowing the repeater device 1210 to be bi-directional.

In an embodiment, repeater device 1210 can be placed at locations wherethere are discontinuities or obstacles on the wire 1202 or othertransmission medium. In the case where the wire 1202 is a power line,these obstacles can include transformers, connections, utility poles,and other such power line devices. The repeater device 1210 can help theguided (e.g., surface) waves jump over these obstacles on the line andboost the transmission power at the same time. In other embodiments, acoupler can be used to jump over the obstacle without the use of arepeater device. In that embodiment, both ends of the coupler can betied or fastened to the wire, thus providing a path for the guided waveto travel without being blocked by the obstacle.

Turning now to FIG. 13, illustrated is a block diagram 1300 of anexample, non-limiting embodiment of a bidirectional repeater inaccordance with various aspects described herein. In particular, abidirectional repeater device 1306 is presented for use in atransmission device, such as transmission device 101 or 102 presented inconjunction with FIG. 1. It should be noted that while the couplers areillustrated as stub couplers, any other of the coupler designs describedherein including arc couplers, antenna or horn couplers, magneticcouplers, or the like, could likewise be used. The bidirectionalrepeater 1306 can employ diversity paths in the case of when two or morewires or other transmission media are present. Since guided wavetransmissions have different transmission efficiencies and couplingefficiencies for transmission medium of different types such asinsulated wires, un-insulated wires or other types of transmission mediaand further, if exposed to the elements, can be affected by weather, andother atmospheric conditions, it can be advantageous to selectivelytransmit on different transmission media at certain times. In variousembodiments, the various transmission media can be designated as aprimary, secondary, tertiary, etc. whether or not such designationindicates a preference of one transmission medium over another.

In the embodiment shown, the transmission media include an insulated oruninsulated wire 1302 and an insulated or uninsulated wire 1304(referred to herein as wires 1302 and 1304, respectively). The repeaterdevice 1306 uses a receiver coupler 1308 to receive a guided wavetraveling along wire 1302 and repeats the transmission using transmitterwaveguide 1310 as a guided wave along wire 1304. In other embodiments,repeater device 1306 can switch from the wire 1304 to the wire 1302, orcan repeat the transmissions along the same paths. Repeater device 1306can include sensors, or be in communication with sensors (or a networkmanagement system 1601 depicted in FIG. 16A) that indicate conditionsthat can affect the transmission. Based on the feedback received fromthe sensors, the repeater device 1306 can make the determination aboutwhether to keep the transmission along the same wire, or transfer thetransmission to the other wire.

Turning now to FIG. 14, illustrated is a block diagram 1400 illustratingan example, non-limiting embodiment of a bidirectional repeater system.In particular, a bidirectional repeater system is presented for use in atransmission device, such as transmission device 101 or 102 presented inconjunction with FIG. 1. The bidirectional repeater system includeswaveguide coupling devices 1402 and 1404 that receive and transmittransmissions from other coupling devices located in a distributedantenna system or backhaul system.

In various embodiments, waveguide coupling device 1402 can receive atransmission from another waveguide coupling device, wherein thetransmission has a plurality of subcarriers. Diplexer 1406 can separatethe transmission from other transmissions, and direct the transmissionto low-noise amplifier (“LNA”) 1408. A frequency mixer 1428, with helpfrom a local oscillator 1412, can downshift the transmission (which isin the millimeter-wave band or around 38 GHz in some embodiments) to alower frequency, such as a cellular band (˜1.9 GHz) for a distributedantenna system, a native frequency, or other frequency for a backhaulsystem. An extractor (or demultiplexer) 1432 can extract the signal on asubcarrier and direct the signal to an output component 1422 foroptional amplification, buffering or isolation by power amplifier 1424for coupling to communications interface 205. The communicationsinterface 205 can further process the signals received from the poweramplifier 1424 or otherwise transmit such signals over a wireless orwired interface to other devices such as a base station, mobile devices,a building, etc. For the signals that are not being extracted at thislocation, extractor 1432 can redirect them to another frequency mixer1436, where the signals are used to modulate a carrier wave generated bylocal oscillator 1414. The carrier wave, with its subcarriers, isdirected to a power amplifier (“PA”) 1416 and is retransmitted bywaveguide coupling device 1404 to another system, via diplexer 1420.

An LNA 1426 can be used to amplify, buffer or isolate signals that arereceived by the communication interface 205 and then send the signal toa multiplexer 1434 which merges the signal with signals that have beenreceived from waveguide coupling device 1404. The signals received fromcoupling device 1404 have been split by diplexer 1420, and then passedthrough LNA 1418, and downshifted in frequency by frequency mixer 1438.When the signals are combined by multiplexer 1434, they are upshifted infrequency by frequency mixer 1430, and then boosted by PA 1410, andtransmitted to another system by waveguide coupling device 1402. In anembodiment bidirectional repeater system can be merely a repeaterwithout the output device 1422. In this embodiment, the multiplexer 1434would not be utilized and signals from LNA 1418 would be directed tomixer 1430 as previously described. It will be appreciated that in someembodiments, the bidirectional repeater system could also be implementedusing two distinct and separate unidirectional repeaters. In analternative embodiment, a bidirectional repeater system could also be abooster or otherwise perform retransmissions without downshifting andupshifting. Indeed in example embodiment, the retransmissions can bebased upon receiving a signal or guided wave and performing some signalor guided wave processing or reshaping, filtering, and/or amplification,prior to retransmission of the signal or guided wave.

Referring now to FIG. 15, a block diagram 1500 illustrating an example,non-limiting embodiment of a guided wave communications system is shown.This diagram depicts an exemplary environment in which a guided wavecommunication system, such as the guided wave communication systempresented in conjunction with FIG. 1, can be used.

To provide network connectivity to additional base station devices, abackhaul network that links the communication cells (e.g., macrocellsand macrocells) to network devices of a core network correspondinglyexpands. Similarly, to provide network connectivity to a distributedantenna system, an extended communication system that links base stationdevices and their distributed antennas is desirable. A guided wavecommunication system 1500 such as shown in FIG. 15 can be provided toenable alternative, increased or additional network connectivity and awaveguide coupling system can be provided to transmit and/or receiveguided wave (e.g., surface wave) communications on a transmission mediumsuch as a wire that operates as a single-wire transmission line (e.g., autility line), and that can be used as a waveguide and/or that otherwiseoperates to guide the transmission of an electromagnetic wave.

The guided wave communication system 1500 can comprise a first instanceof a distribution system 1550 that includes one or more base stationdevices (e.g., base station device 1504) that are communicably coupledto a central office 1501 and/or a macrocell site 1502. Base stationdevice 1504 can be connected by a wired (e.g., fiber and/or cable), orby a wireless (e.g., microwave wireless) connection to the macrocellsite 1502 and the central office 1501. A second instance of thedistribution system 1560 can be used to provide wireless voice and dataservices to mobile device 1522 and to residential and/or commercialestablishments 1542 (herein referred to as establishments 1542). System1500 can have additional instances of the distribution systems 1550 and1560 for providing voice and/or data services to mobile devices1522-1524 and establishments 1542 as shown in FIG. 15.

Macrocells such as macrocell site 1502 can have dedicated connections toa mobile network and base station device 1504 or can share and/orotherwise use another connection. Central office 1501 can be used todistribute media content and/or provide internet service provider (ISP)services to mobile devices 1522-1524 and establishments 1542. Thecentral office 1501 can receive media content from a constellation ofsatellites 1530 (one of which is shown in FIG. 15) or other sources ofcontent, and distribute such content to mobile devices 1522-1524 andestablishments 1542 via the first and second instances of thedistribution system 1550 and 1560. The central office 1501 can also becommunicatively coupled to the Internet 1503 for providing internet dataservices to mobile devices 1522-1524 and establishments 1542.

Base station device 1504 can be mounted on, or attached to, utility pole1516. In other embodiments, base station device 1504 can be neartransformers and/or other locations situated nearby a power line. Basestation device 1504 can facilitate connectivity to a mobile network formobile devices 1522 and 1524. Antennas 1512 and 1514, mounted on or nearutility poles 1518 and 1520, respectively, can receive signals from basestation device 1504 and transmit those signals to mobile devices 1522and 1524 over a much wider area than if the antennas 1512 and 1514 werelocated at or near base station device 1504.

It is noted that FIG. 15 displays three utility poles, in each instanceof the distribution systems 1550 and 1560, with one base station device,for purposes of simplicity. In other embodiments, utility pole 1516 canhave more base station devices, and more utility poles with distributedantennas and/or tethered connections to establishments 1542.

A transmission device 1506, such as transmission device 101 or 102presented in conjunction with FIG. 1, can transmit a signal from basestation device 1504 to antennas 1512 and 1514 via utility or powerline(s) that connect the utility poles 1516, 1518, and 1520. To transmitthe signal, radio source and/or transmission device 1506 upconverts thesignal (e.g., via frequency mixing) from base station device 1504 orotherwise converts the signal from the base station device 1504 to amicrowave band signal and the transmission device 1506 launches amicrowave band wave that propagates as a guided wave traveling along theutility line or other wire as described in previous embodiments. Atutility pole 1518, another transmission device 1508 receives the guidedwave (and optionally can amplify it as needed or desired or operate as arepeater to receive it and regenerate it) and sends it forward as aguided wave on the utility line or other wire. The transmission device1508 can also extract a signal from the microwave band guided wave andshift it down in frequency or otherwise convert it to its originalcellular band frequency (e.g., 1.9 GHz or other defined cellularfrequency) or another cellular (or non-cellular) band frequency. Anantenna 1512 can wireless transmit the downshifted signal to mobiledevice 1522. The process can be repeated by transmission device 1510,antenna 1514 and mobile device 1524, as necessary or desirable.

Transmissions from mobile devices 1522 and 1524 can also be received byantennas 1512 and 1514 respectively. The transmission devices 1508 and1510 can upshift or otherwise convert the cellular band signals tomicrowave band and transmit the signals as guided wave (e.g., surfacewave or other electromagnetic wave) transmissions over the power line(s)to base station device 1504.

Media content received by the central office 1501 can be supplied to thesecond instance of the distribution system 1560 via the base stationdevice 1504 for distribution to mobile devices 1522 and establishments1542. The transmission device 1510 can be tethered to the establishments1542 by one or more wired connections or a wireless interface. The oneor more wired connections may include without limitation, a power line,a coaxial cable, a fiber cable, a twisted pair cable, a guided wavetransmission medium or other suitable wired mediums for distribution ofmedia content and/or for providing internet services. In an exampleembodiment, the wired connections from the transmission device 1510 canbe communicatively coupled to one or more very high bit rate digitalsubscriber line (VDSL) modems located at one or more correspondingservice area interfaces (SAIs—not shown) or pedestals, each SAI orpedestal providing services to a portion of the establishments 1542. TheVDSL modems can be used to selectively distribute media content and/orprovide internet services to gateways (not shown) located in theestablishments 1542. The SAIs or pedestals can also be communicativelycoupled to the establishments 1542 over a wired medium such as a powerline, a coaxial cable, a fiber cable, a twisted pair cable, a guidedwave transmission medium or other suitable wired mediums. In otherexample embodiments, the transmission device 1510 can be communicativelycoupled directly to establishments 1542 without intermediate interfacessuch as the SAIs or pedestals.

In another example embodiment, system 1500 can employ diversity paths,where two or more utility lines or other wires are strung between theutility poles 1516, 1518, and 1520 (e.g., for example, two or more wiresbetween poles 1516 and 1520) and redundant transmissions from basestation/macrocell site 1502 are transmitted as guided waves down thesurface of the utility lines or other wires. The utility lines or otherwires can be either insulated or uninsulated, and depending on theenvironmental conditions that cause transmission losses, the couplingdevices can selectively receive signals from the insulated oruninsulated utility lines or other wires. The selection can be based onmeasurements of the signal-to-noise ratio of the wires, or based ondetermined weather/environmental conditions (e.g., moisture detectors,weather forecasts, etc.). The use of diversity paths with system 1500can enable alternate routing capabilities, load balancing, increasedload handling, concurrent bi-directional or synchronous communications,spread spectrum communications, etc.

It is noted that the use of the transmission devices 1506, 1508, and1510 in FIG. 15 are by way of example only, and that in otherembodiments, other uses are possible. For instance, transmission devicescan be used in a backhaul communication system, providing networkconnectivity to base station devices. Transmission devices 1506, 1508,and 1510 can be used in many circumstances where it is desirable totransmit guided wave communications over a wire, whether insulated ornot insulated. Transmission devices 1506, 1508, and 1510 areimprovements over other coupling devices due to no contact or limitedphysical and/or electrical contact with the wires that may carry highvoltages. The transmission device can be located away from the wire(e.g., spaced apart from the wire) and/or located on the wire so long asit is not electrically in contact with the wire, as the dielectric actsas an insulator, allowing for cheap, easy, and/or less complexinstallation. However, as previously noted conducting or non-dielectriccouplers can be employed, for example in configurations where the wirescorrespond to a telephone network, cable television network, broadbanddata service, fiber optic communications system or other networkemploying low voltages or having insulated transmission lines.

It is further noted, that while base station device 1504 and macrocellsite 1502 are illustrated in an embodiment, other network configurationsare likewise possible. For example, devices such as access points orother wireless gateways can be employed in a similar fashion to extendthe reach of other networks such as a wireless local area network, awireless personal area network or other wireless network that operatesin accordance with a communication protocol such as a 802.11 protocol,WIMAX protocol, UltraWideband protocol, Bluetooth® protocol, Zigbee®protocol or other wireless protocol.

Referring now to FIGS. 16A & 16B, block diagrams illustrating anexample, non-limiting embodiment of a system for managing a power gridcommunication system are shown. Considering FIG. 16A, a waveguide system1602 is presented for use in a guided wave communications system 1600,such as the system presented in conjunction with FIG. 15. The waveguidesystem 1602 can comprise sensors 1604, a power management system 1605, atransmission device 101 or 102 that includes at least one communicationinterface 205, transceiver 210 and coupler 220.

The waveguide system 1602 can be coupled to a power line 1610 forfacilitating guided wave communications in accordance with embodimentsdescribed in the subject disclosure. In an example embodiment, thetransmission device 101 or 102 includes coupler 220 for inducingelectromagnetic waves on a surface of the power line 1610 thatlongitudinally propagate along the surface of the power line 1610 asdescribed in the subject disclosure. The transmission device 101 or 102can also serve as a repeater for retransmitting electromagnetic waves onthe same power line 1610 or for routing electromagnetic waves betweenpower lines 1610 as shown in FIGS. 12-13.

The transmission device 101 or 102 includes transceiver 210 configuredto, for example, up-convert a signal operating at an original frequencyrange to electromagnetic waves operating at, exhibiting, or associatedwith a carrier frequency that propagate along a coupler to inducecorresponding guided electromagnetic waves that propagate along asurface of the power line 1610. A carrier frequency can be representedby a center frequency having upper and lower cutoff frequencies thatdefine the bandwidth of the electromagnetic waves. The power line 1610can be a wire (e.g., single stranded or multi-stranded) having aconducting surface or insulated surface. The transceiver 210 can alsoreceive signals from the coupler 220 and down-convert theelectromagnetic waves operating at a carrier frequency to signals attheir original frequency.

Signals received by the communications interface 205 of transmissiondevice 101 or 102 for up-conversion can include without limitationsignals supplied by a central office 1611 over a wired or wirelessinterface of the communications interface 205, a base station 1614 overa wired or wireless interface of the communications interface 205,wireless signals transmitted by mobile devices 1620 to the base station1614 for delivery over the wired or wireless interface of thecommunications interface 205, signals supplied by in-buildingcommunication devices 1618 over the wired or wireless interface of thecommunications interface 205, and/or wireless signals supplied to thecommunications interface 205 by mobile devices 1612 roaming in awireless communication range of the communications interface 205. Inembodiments where the waveguide system 1602 functions as a repeater,such as shown in FIGS. 12-13, the communications interface 205 may ormay not be included in the waveguide system 1602.

The electromagnetic waves propagating along the surface of the powerline 1610 can be modulated and formatted to include packets or frames ofdata that include a data payload and further include networkinginformation (such as header information for identifying one or moredestination waveguide systems 1602). The networking information may beprovided by the waveguide system 1602 or an originating device such asthe central office 1611, the base station 1614, mobile devices 1620, orin-building devices 1618, or a combination thereof. Additionally, themodulated electromagnetic waves can include error correction data formitigating signal disturbances. The networking information and errorcorrection data can be used by a destination waveguide system 1602 fordetecting transmissions directed to it, and for down-converting andprocessing with error correction data transmissions that include voiceand/or data signals directed to recipient communication devicescommunicatively coupled to the destination waveguide system 1602.

Referring now to the sensors 1604 of the waveguide system 1602, thesensors 1604 can comprise one or more of a temperature sensor 1604 a, adisturbance detection sensor 1604 b, a loss of energy sensor 1604 c, anoise sensor 1604 d, a vibration sensor 1604 e, an environmental (e.g.,weather) sensor 1604 f, and/or an image sensor 1604 g. The temperaturesensor 1604 a can be used to measure ambient temperature, a temperatureof the transmission device 101 or 102, a temperature of the power line1610, temperature differentials (e.g., compared to a setpoint orbaseline, between transmission device 101 or 102 and 1610, etc.), or anycombination thereof. In one embodiment, temperature metrics can becollected and reported periodically to a network management system 1601by way of the base station 1614.

The disturbance detection sensor 1604 b can perform measurements on thepower line 1610 to detect disturbances such as signal reflections, whichmay indicate a presence of a downstream disturbance that may impede thepropagation of electromagnetic waves on the power line 1610. A signalreflection can represent a distortion resulting from, for example, anelectromagnetic wave transmitted on the power line 1610 by thetransmission device 101 or 102 that reflects in whole or in part back tothe transmission device 101 or 102 from a disturbance in the power line1610 located downstream from the transmission device 101 or 102.

Signal reflections can be caused by obstructions on the power line 1610.For example, a tree limb may cause electromagnetic wave reflections whenthe tree limb is lying on the power line 1610, or is in close proximityto the power line 1610 which may cause a corona discharge. Otherobstructions that can cause electromagnetic wave reflections can includewithout limitation an object that has been entangled on the power line1610 (e.g., clothing, a shoe wrapped around a power line 1610 with ashoe string, etc.), a corroded build-up on the power line 1610 or an icebuild-up. Power grid components may also impede or obstruct with thepropagation of electromagnetic waves on the surface of power lines 1610.Illustrations of power grid components that may cause signal reflectionsinclude without limitation a transformer and a joint for connectingspliced power lines. A sharp angle on the power line 1610 may also causeelectromagnetic wave reflections.

The disturbance detection sensor 1604 b can comprise a circuit tocompare magnitudes of electromagnetic wave reflections to magnitudes oforiginal electromagnetic waves transmitted by the transmission device101 or 102 to determine how much a downstream disturbance in the powerline 1610 attenuates transmissions. The disturbance detection sensor1604 b can further comprise a spectral analyzer circuit for performingspectral analysis on the reflected waves. The spectral data generated bythe spectral analyzer circuit can be compared with spectral profiles viapattern recognition, an expert system, curve fitting, matched filteringor other artificial intelligence, classification or comparison techniqueto identify a type of disturbance based on, for example, the spectralprofile that most closely matches the spectral data. The spectralprofiles can be stored in a memory of the disturbance detection sensor1604 b or may be remotely accessible by the disturbance detection sensor1604 b. The profiles can comprise spectral data that models differentdisturbances that may be encountered on power lines 1610 to enable thedisturbance detection sensor 1604 b to identify disturbances locally. Anidentification of the disturbance if known can be reported to thenetwork management system 1601 by way of the base station 1614. Thedisturbance detection sensor 1604 b can also utilize the transmissiondevice 101 or 102 to transmit electromagnetic waves as test signals todetermine a roundtrip time for an electromagnetic wave reflection. Theround trip time measured by the disturbance detection sensor 1604 b canbe used to calculate a distance traveled by the electromagnetic wave upto a point where the reflection takes place, which enables thedisturbance detection sensor 1604 b to calculate a distance from thetransmission device 101 or 102 to the downstream disturbance on thepower line 1610.

The distance calculated can be reported to the network management system1601 by way of the base station 1614. In one embodiment, the location ofthe waveguide system 1602 on the power line 1610 may be known to thenetwork management system 1601, which the network management system 1601can use to determine a location of the disturbance on the power line1610 based on a known topology of the power grid. In another embodiment,the waveguide system 1602 can provide its location to the networkmanagement system 1601 to assist in the determination of the location ofthe disturbance on the power line 1610. The location of the waveguidesystem 1602 can be obtained by the waveguide system 1602 from apre-programmed location of the waveguide system 1602 stored in a memoryof the waveguide system 1602, or the waveguide system 1602 can determineits location using a GPS receiver (not shown) included in the waveguidesystem 1602.

The power management system 1605 provides energy to the aforementionedcomponents of the waveguide system 1602. The power management system1605 can receive energy from solar cells, or from a transformer (notshown) coupled to the power line 1610, or by inductive coupling to thepower line 1610 or another nearby power line. The power managementsystem 1605 can also include a backup battery and/or a super capacitoror other capacitor circuit for providing the waveguide system 1602 withtemporary power. The loss of energy sensor 1604 c can be used to detectwhen the waveguide system 1602 has a loss of power condition and/or theoccurrence of some other malfunction. For example, the loss of energysensor 1604 c can detect when there is a loss of power due to defectivesolar cells, an obstruction on the solar cells that causes them tomalfunction, loss of power on the power line 1610, and/or when thebackup power system malfunctions due to expiration of a backup battery,or a detectable defect in a super capacitor. When a malfunction and/orloss of power occurs, the loss of energy sensor 1604 c can notify thenetwork management system 1601 by way of the base station 1614.

The noise sensor 1604 d can be used to measure noise on the power line1610 that may adversely affect transmission of electromagnetic waves onthe power line 1610. The noise sensor 1604 d can sense unexpectedelectromagnetic interference, noise bursts, or other sources ofdisturbances that may interrupt reception of modulated electromagneticwaves on a surface of a power line 1610. A noise burst can be caused by,for example, a corona discharge, or other source of noise. The noisesensor 1604 d can compare the measured noise to a noise profile obtainedby the waveguide system 1602 from an internal database of noise profilesor from a remotely located database that stores noise profiles viapattern recognition, an expert system, curve fitting, matched filteringor other artificial intelligence, classification or comparisontechnique. From the comparison, the noise sensor 1604 d may identify anoise source (e.g., corona discharge or otherwise) based on, forexample, the noise profile that provides the closest match to themeasured noise. The noise sensor 1604 d can also detect how noiseaffects transmissions by measuring transmission metrics such as biterror rate, packet loss rate, jitter, packet retransmission requests,etc. The noise sensor 1604 d can report to the network management system1601 by way of the base station 1614 the identity of noise sources,their time of occurrence, and transmission metrics, among other things.

The vibration sensor 1604 e can include accelerometers and/or gyroscopesto detect 2D or 3D vibrations on the power line 1610. The vibrations canbe compared to vibration profiles that can be stored locally in thewaveguide system 1602, or obtained by the waveguide system 1602 from aremote database via pattern recognition, an expert system, curvefitting, matched filtering or other artificial intelligence,classification or comparison technique. Vibration profiles can be used,for example, to distinguish fallen trees from wind gusts based on, forexample, the vibration profile that provides the closest match to themeasured vibrations. The results of this analysis can be reported by thevibration sensor 1604 e to the network management system 1601 by way ofthe base station 1614.

The environmental sensor 1604 f can include a barometer for measuringatmospheric pressure, ambient temperature (which can be provided by thetemperature sensor 1604 a), wind speed, humidity, wind direction, andrainfall, among other things. The environmental sensor 1604 f cancollect raw information and process this information by comparing it toenvironmental profiles that can be obtained from a memory of thewaveguide system 1602 or a remote database to predict weather conditionsbefore they arise via pattern recognition, an expert system,knowledge-based system or other artificial intelligence, classificationor other weather modeling and prediction technique. The environmentalsensor 1604 f can report raw data as well as its analysis to the networkmanagement system 1601.

The image sensor 1604 g can be a digital camera (e.g., a charged coupleddevice or CCD imager, infrared camera, etc.) for capturing images in avicinity of the waveguide system 1602. The image sensor 1604 g caninclude an electromechanical mechanism to control movement (e.g., actualposition or focal points/zooms) of the camera for inspecting the powerline 1610 from multiple perspectives (e.g., top surface, bottom surface,left surface, right surface and so on). Alternatively, the image sensor1604 g can be designed such that no electromechanical mechanism isneeded in order to obtain the multiple perspectives. The collection andretrieval of imaging data generated by the image sensor 1604 g can becontrolled by the network management system 1601, or can be autonomouslycollected and reported by the image sensor 1604 g to the networkmanagement system 1601.

Other sensors that may be suitable for collecting telemetry informationassociated with the waveguide system 1602 and/or the power lines 1610for purposes of detecting, predicting and/or mitigating disturbancesthat can impede the propagation of electromagnetic wave transmissions onpower lines 1610 (or any other form of a transmission medium ofelectromagnetic waves) may be utilized by the waveguide system 1602.

Referring now to FIG. 16B, block diagram 1650 illustrates an example,non-limiting embodiment of a system for managing a power grid 1653 and acommunication system 1655 embedded therein or associated therewith inaccordance with various aspects described herein. The communicationsystem 1655 comprises a plurality of waveguide systems 1602 coupled topower lines 1610 of the power grid 1653. At least a portion of thewaveguide systems 1602 used in the communication system 1655 can be indirect communication with a base station 1614 and/or the networkmanagement system 1601. Waveguide systems 1602 not directly connected toa base station 1614 or the network management system 1601 can engage incommunication sessions with either a base station 1614 or the networkmanagement system 1601 by way of other downstream waveguide systems 1602connected to a base station 1614 or the network management system 1601.

The network management system 1601 can be communicatively coupled toequipment of a utility company 1652 and equipment of a communicationsservice provider 1654 for providing each entity, status informationassociated with the power grid 1653 and the communication system 1655,respectively. The network management system 1601, the equipment of theutility company 1652, and the communications service provider 1654 canaccess communication devices utilized by utility company personnel 1656and/or communication devices utilized by communications service providerpersonnel 1658 for purposes of providing status information and/or fordirecting such personnel in the management of the power grid 1653 and/orcommunication system 1655.

FIG. 17A illustrates a flow diagram of an example, non-limitingembodiment of a method 1700 for detecting and mitigating disturbancesoccurring in a communication network of the systems of FIGS. 16A & 16B.Method 1700 can begin with step 1702 where a waveguide system 1602transmits and receives messages embedded in, or forming part of,modulated electromagnetic waves or another type of electromagnetic wavestraveling along a surface of a power line 1610. The messages can bevoice messages, streaming video, and/or other data/information exchangedbetween communication devices communicatively coupled to thecommunication system 1655. At step 1704 the sensors 1604 of thewaveguide system 1602 can collect sensing data. In an embodiment, thesensing data can be collected in step 1704 prior to, during, or afterthe transmission and/or receipt of messages in step 1702. At step 1706the waveguide system 1602 (or the sensors 1604 themselves) can determinefrom the sensing data an actual or predicted occurrence of a disturbancein the communication system 1655 that can affect communicationsoriginating from (e.g., transmitted by) or received by the waveguidesystem 1602. The waveguide system 1602 (or the sensors 1604) can processtemperature data, signal reflection data, loss of energy data, noisedata, vibration data, environmental data, or any combination thereof tomake this determination. The waveguide system 1602 (or the sensors 1604)may also detect, identify, estimate, or predict the source of thedisturbance and/or its location in the communication system 1655. If adisturbance is neither detected/identified nor predicted/estimated atstep 1708, the waveguide system 1602 can proceed to step 1702 where itcontinues to transmit and receive messages embedded in, or forming partof, modulated electromagnetic waves traveling along a surface of thepower line 1610.

If at step 1708 a disturbance is detected/identified orpredicted/estimated to occur, the waveguide system 1602 proceeds to step1710 to determine if the disturbance adversely affects (oralternatively, is likely to adversely affect or the extent to which itmay adversely affect) transmission or reception of messages in thecommunication system 1655. In one embodiment, a duration threshold and afrequency of occurrence threshold can be used at step 1710 to determinewhen a disturbance adversely affects communications in the communicationsystem 1655. For illustration purposes only, assume a duration thresholdis set to 500 ms, while a frequency of occurrence threshold is set to 5disturbances occurring in an observation period of 10 sec. Thus, adisturbance having a duration greater than 500 ms will trigger theduration threshold. Additionally, any disturbance occurring more than 5times in a 10 sec time interval will trigger the frequency of occurrencethreshold.

In one embodiment, a disturbance may be considered to adversely affectsignal integrity in the communication systems 1655 when the durationthreshold alone is exceeded. In another embodiment, a disturbance may beconsidered as adversely affecting signal integrity in the communicationsystems 1655 when both the duration threshold and the frequency ofoccurrence threshold are exceeded. The latter embodiment is thus moreconservative than the former embodiment for classifying disturbancesthat adversely affect signal integrity in the communication system 1655.It will be appreciated that many other algorithms and associatedparameters and thresholds can be utilized for step 1710 in accordancewith example embodiments.

Referring back to method 1700, if at step 1710 the disturbance detectedat step 1708 does not meet the condition for adversely affectedcommunications (e.g., neither exceeds the duration threshold nor thefrequency of occurrence threshold), the waveguide system 1602 mayproceed to step 1702 and continue processing messages. For instance, ifthe disturbance detected in step 1708 has a duration of 1 msec with asingle occurrence in a 10 sec time period, then neither threshold willbe exceeded. Consequently, such a disturbance may be considered ashaving a nominal effect on signal integrity in the communication system1655 and thus would not be flagged as a disturbance requiringmitigation. Although not flagged, the occurrence of the disturbance, itstime of occurrence, its frequency of occurrence, spectral data, and/orother useful information, may be reported to the network managementsystem 1601 as telemetry data for monitoring purposes.

Referring back to step 1710, if on the other hand the disturbancesatisfies the condition for adversely affected communications (e.g.,exceeds either or both thresholds), the waveguide system 1602 canproceed to step 1712 and report the incident to the network managementsystem 1601. The report can include raw sensing data collected by thesensors 1604, a description of the disturbance if known by the waveguidesystem 1602, a time of occurrence of the disturbance, a frequency ofoccurrence of the disturbance, a location associated with thedisturbance, parameters readings such as bit error rate, packet lossrate, retransmission requests, jitter, latency and so on. If thedisturbance is based on a prediction by one or more sensors of thewaveguide system 1602, the report can include a type of disturbanceexpected, and if predictable, an expected time occurrence of thedisturbance, and an expected frequency of occurrence of the predicteddisturbance when the prediction is based on historical sensing datacollected by the sensors 1604 of the waveguide system 1602.

At step 1714, the network management system 1601 can determine amitigation, circumvention, or correction technique, which may includedirecting the waveguide system 1602 to reroute traffic to circumvent thedisturbance if the location of the disturbance can be determined. In oneembodiment, the waveguide coupling device 1402 detecting the disturbancemay direct a repeater such as the one shown in FIGS. 13-14 to connectthe waveguide system 1602 from a primary power line affected by thedisturbance to a secondary power line to enable the waveguide system1602 to reroute traffic to a different transmission medium and avoid thedisturbance. In an embodiment where the waveguide system 1602 isconfigured as a repeater the waveguide system 1602 can itself performthe rerouting of traffic from the primary power line to the secondarypower line. It is further noted that for bidirectional communications(e.g., full or half-duplex communications), the repeater can beconfigured to reroute traffic from the secondary power line back to theprimary power line for processing by the waveguide system 1602.

In another embodiment, the waveguide system 1602 can redirect traffic byinstructing a first repeater situated upstream of the disturbance and asecond repeater situated downstream of the disturbance to redirecttraffic from a primary power line temporarily to a secondary power lineand back to the primary power line in a manner that avoids thedisturbance. It is further noted that for bidirectional communications(e.g., full or half-duplex communications), repeaters can be configuredto reroute traffic from the secondary power line back to the primarypower line.

To avoid interrupting existing communication sessions occurring on asecondary power line, the network management system 1601 may direct thewaveguide system 1602 to instruct repeater(s) to utilize unused timeslot(s) and/or frequency band(s) of the secondary power line forredirecting data and/or voice traffic away from the primary power lineto circumvent the disturbance.

At step 1716, while traffic is being rerouted to avoid the disturbance,the network management system 1601 can notify equipment of the utilitycompany 1652 and/or equipment of the communications service provider1654, which in turn may notify personnel of the utility company 1656and/or personnel of the communications service provider 1658 of thedetected disturbance and its location if known. Field personnel fromeither party can attend to resolving the disturbance at a determinedlocation of the disturbance. Once the disturbance is removed orotherwise mitigated by personnel of the utility company and/or personnelof the communications service provider, such personnel can notify theirrespective companies and/or the network management system 1601 utilizingfield equipment (e.g., a laptop computer, smartphone, etc.)communicatively coupled to network management system 1601, and/orequipment of the utility company and/or the communications serviceprovider. The notification can include a description of how thedisturbance was mitigated and any changes to the power lines 1610 thatmay change a topology of the communication system 1655.

Once the disturbance has been resolved (as determined in decision 1718),the network management system 1601 can direct the waveguide system 1602at step 1720 to restore the previous routing configuration used by thewaveguide system 1602 or route traffic according to a new routingconfiguration if the restoration strategy used to mitigate thedisturbance resulted in a new network topology of the communicationsystem 1655. In another embodiment, the waveguide system 1602 can beconfigured to monitor mitigation of the disturbance by transmitting testsignals on the power line 1610 to determine when the disturbance hasbeen removed. Once the waveguide system 1602 detects an absence of thedisturbance it can autonomously restore its routing configurationwithout assistance by the network management system 1601 if itdetermines the network topology of the communication system 1655 has notchanged, or it can utilize a new routing configuration that adapts to adetected new network topology.

FIG. 17B illustrates a flow diagram of an example, non-limitingembodiment of a method 1750 for detecting and mitigating disturbancesoccurring in a communication network of the system of FIGS. 16A and 16B.In one embodiment, method 1750 can begin with step 1752 where a networkmanagement system 1601 receives from equipment of the utility company1652 or equipment of the communications service provider 1654maintenance information associated with a maintenance schedule. Thenetwork management system 1601 can at step 1754 identify from themaintenance information, maintenance activities to be performed duringthe maintenance schedule. From these activities, the network managementsystem 1601 can detect a disturbance resulting from the maintenance(e.g., scheduled replacement of a power line 1610, scheduled replacementof a waveguide system 1602 on the power line 1610, scheduledreconfiguration of power lines 1610 in the power grid 1653, etc.).

In another embodiment, the network management system 1601 can receive atstep 1755 telemetry information from one or more waveguide systems 1602.The telemetry information can include among other things an identity ofeach waveguide system 1602 submitting the telemetry information,measurements taken by sensors 1604 of each waveguide system 1602,information relating to predicted, estimated, or actual disturbancesdetected by the sensors 1604 of each waveguide system 1602, locationinformation associated with each waveguide system 1602, an estimatedlocation of a detected disturbance, an identification of thedisturbance, and so on. The network management system 1601 can determinefrom the telemetry information a type of disturbance that may be adverseto operations of the waveguide, transmission of the electromagneticwaves along the wire surface, or both. The network management system1601 can also use telemetry information from multiple waveguide systems1602 to isolate and identify the disturbance. Additionally, the networkmanagement system 1601 can request telemetry information from waveguidesystems 1602 in a vicinity of an affected waveguide system 1602 totriangulate a location of the disturbance and/or validate anidentification of the disturbance by receiving similar telemetryinformation from other waveguide systems 1602.

In yet another embodiment, the network management system 1601 canreceive at step 1756 an unscheduled activity report from maintenancefield personnel. Unscheduled maintenance may occur as result of fieldcalls that are unplanned or as a result of unexpected field issuesdiscovered during field calls or scheduled maintenance activities. Theactivity report can identify changes to a topology configuration of thepower grid 1653 resulting from field personnel addressing discoveredissues in the communication system 1655 and/or power grid 1653, changesto one or more waveguide systems 1602 (such as replacement or repairthereof), mitigation of disturbances performed if any, and so on.

At step 1758, the network management system 1601 can determine fromreports received according to steps 1752 through 1756 if a disturbancewill occur based on a maintenance schedule, or if a disturbance hasoccurred or is predicted to occur based on telemetry data, or if adisturbance has occurred due to an unplanned maintenance identified in afield activity report. From any of these reports, the network managementsystem 1601 can determine whether a detected or predicted disturbancerequires rerouting of traffic by the affected waveguide systems 1602 orother waveguide systems 1602 of the communication system 1655.

When a disturbance is detected or predicted at step 1758, the networkmanagement system 1601 can proceed to step 1760 where it can direct oneor more waveguide systems 1602 to reroute traffic to circumvent thedisturbance. When the disturbance is permanent due to a permanenttopology change of the power grid 1653, the network management system1601 can proceed to step 1770 and skip steps 1762, 1764, 1766, and 1772.At step 1770, the network management system 1601 can direct one or morewaveguide systems 1602 to use a new routing configuration that adapts tothe new topology. However, when the disturbance has been detected fromtelemetry information supplied by one or more waveguide systems 1602,the network management system 1601 can notify maintenance personnel ofthe utility company 1656 or the communications service provider 1658 ofa location of the disturbance, a type of disturbance if known, andrelated information that may be helpful to such personnel to mitigatethe disturbance. When a disturbance is expected due to maintenanceactivities, the network management system 1601 can direct one or morewaveguide systems 1602 to reconfigure traffic routes at a given schedule(consistent with the maintenance schedule) to avoid disturbances causedby the maintenance activities during the maintenance schedule.

Returning back to step 1760 and upon its completion, the process cancontinue with step 1762. At step 1762, the network management system1601 can monitor when the disturbance(s) have been mitigated by fieldpersonnel. Mitigation of a disturbance can be detected at step 1762 byanalyzing field reports submitted to the network management system 1601by field personnel over a communications network (e.g., cellularcommunication system) utilizing field equipment (e.g., a laptop computeror handheld computer/device). If field personnel have reported that adisturbance has been mitigated, the network management system 1601 canproceed to step 1764 to determine from the field report whether atopology change was required to mitigate the disturbance. A topologychange can include rerouting a power line 1610, reconfiguring awaveguide system 1602 to utilize a different power line 1610, otherwiseutilizing an alternative link to bypass the disturbance and so on. If atopology change has taken place, the network management system 1601 candirect at step 1770 one or more waveguide systems 1602 to use a newrouting configuration that adapts to the new topology.

If, however, a topology change has not been reported by field personnel,the network management system 1601 can proceed to step 1766 where it candirect one or more waveguide systems 1602 to send test signals to test arouting configuration that had been used prior to the detecteddisturbance(s). Test signals can be sent to affected waveguide systems1602 in a vicinity of the disturbance. The test signals can be used todetermine if signal disturbances (e.g., electromagnetic wavereflections) are detected by any of the waveguide systems 1602. If thetest signals confirm that a prior routing configuration is no longersubject to previously detected disturbance(s), then the networkmanagement system 1601 can at step 1772 direct the affected waveguidesystems 1602 to restore a previous routing configuration. If, however,test signals analyzed by one or more waveguide coupling device 1402 andreported to the network management system 1601 indicate that thedisturbance(s) or new disturbance(s) are present, then the networkmanagement system 1601 will proceed to step 1768 and report thisinformation to field personnel to further address field issues. Thenetwork management system 1601 can in this situation continue to monitormitigation of the disturbance(s) at step 1762.

In the aforementioned embodiments, the waveguide systems 1602 can beconfigured to be self-adapting to changes in the power grid 1653 and/orto mitigation of disturbances. That is, one or more affected waveguidesystems 1602 can be configured to self-monitor mitigation ofdisturbances and reconfigure traffic routes without requiringinstructions to be sent to them by the network management system 1601.In this embodiment, the one or more waveguide systems 1602 that areself-configurable can inform the network management system 1601 of itsrouting choices so that the network management system 1601 can maintaina macro-level view of the communication topology of the communicationsystem 1655.

While for purposes of simplicity of explanation, the respectiveprocesses are shown and described as a series of blocks in FIGS. 17A and17B, respectively, it is to be understood and appreciated that theclaimed subject matter is not limited by the order of the blocks, assome blocks may occur in different orders and/or concurrently with otherblocks from what is depicted and described herein. Moreover, not allillustrated blocks may be required to implement the methods describedherein.

Turning now to FIG. 18A, a block diagram illustrating an example,non-limiting embodiment of a transmission medium 1800 for propagatingguided electromagnetic waves is shown. In particular, a further exampleof transmission medium 125 presented in conjunction with FIG. 1 ispresented. In an embodiment, the transmission medium 1800 can comprise afirst dielectric material 1802 and a second dielectric material 1804disposed thereon. In an embodiment, the first dielectric material 1802can comprise a dielectric core (referred to herein as dielectric core1802) and the second dielectric material 1804 can comprise a cladding orshell such as a dielectric foam that surrounds in whole or in part thedielectric core (referred to herein as dielectric foam 1804). In anembodiment, the dielectric core 1802 and dielectric foam 1804 can becoaxially aligned to each other (although not necessary). In anembodiment, the combination of the dielectric core 1802 and thedielectric foam 1804 can be flexed or bent at least by 45 degreeswithout damaging the materials of the dielectric core 1802 and thedielectric foam 1804. In an embodiment, an outer surface of thedielectric foam 1804 can be further surrounded in whole or in part by athird dielectric material 1806, which can serve as an outer jacket(referred to herein as jacket 1806). The jacket 1806 can preventexposure of the dielectric core 1802 and the dielectric foam 1804 to anenvironment that can adversely affect the propagation of electromagneticwaves (e.g., water, soil, etc.).

The dielectric core 1802 can comprise, for example, a high densitypolyethylene material, a high density polyurethane material, or othersuitable dielectric material(s). The dielectric foam 1804 can comprise,for example, a cellular plastic material such an expanded polyethylenematerial, or other suitable dielectric material(s). The jacket 1806 cancomprise, for example, a polyethylene material or equivalent. In anembodiment, the dielectric constant of the dielectric foam 1804 can be(or substantially) lower than the dielectric constant of the dielectriccore 1802. For example, the dielectric constant of the dielectric core1802 can be approximately 2.3 while the dielectric constant of thedielectric foam 1804 can be approximately 1.15 (slightly higher than thedielectric constant of air).

The dielectric core 1802 can be used for receiving signals in the formof electromagnetic waves from a launcher or other coupling devicedescribed herein which can be configured to launch guidedelectromagnetic waves on the transmission medium 1800. In oneembodiment, the transmission 1800 can be coupled to a hollow waveguide1808 structured as, for example, a circular waveguide 1809, which canreceive electromagnetic waves from a radiating device such as a stubantenna (not shown). The hollow waveguide 1808 can in turn induce guidedelectromagnetic waves in the dielectric core 1802. In thisconfiguration, the guided electromagnetic waves are guided by or boundto the dielectric core 1802 and propagate longitudinally along thedielectric core 1802. By adjusting electronics of the launcher, anoperating frequency of the electromagnetic waves can be chosen such thata field intensity profile 1810 of the guided electromagnetic wavesextends nominally (or not at all) outside of the jacket 1806.

By maintaining most (if not all) of the field strength of the guidedelectromagnetic waves within portions of the dielectric core 1802, thedielectric foam 1804 and/or the jacket 1806, the transmission medium1800 can be used in hostile environments without adversely affecting thepropagation of the electromagnetic waves propagating therein. Forexample, the transmission medium 1800 can be buried in soil with no (ornearly no) adverse effect to the guided electromagnetic wavespropagating in the transmission medium 1800. Similarly, the transmissionmedium 1800 can be exposed to water (e.g., rain or placed underwater)with no (or nearly no) adverse effect to the guided electromagneticwaves propagating in the transmission medium 1800. In an embodiment, thepropagation loss of guided electromagnetic waves in the foregoingembodiments can be 1 to 2 dB per meter or better at an operatingfrequency of 60 GHz. Depending on the operating frequency of the guidedelectromagnetic waves and/or the materials used for the transmissionmedium 1800 other propagation losses may be possible. Additionally,depending on the materials used to construct the transmission medium1800, the transmission medium 1800 can in some embodiments be flexedlaterally with no (or nearly no) adverse effect to the guidedelectromagnetic waves propagating through the dielectric core 1802 andthe dielectric foam 1804.

Other configurations of the transmission medium 1800 are possibleincluding, a transmission medium that comprises a conductive core withor without an insulation layer surrounding the conductive core in wholeor in part that is, in turn, covered in whole or in part by a dielectricfoam 1804 and jacket 1806, which can be constructed from the materialspreviously described.

It should be noted that the hollow launcher 1808 used with thetransmission medium 1800 can be replaced with other launchers, couplersor coupling devices described in the subject disclosure. Additionally,the propagation mode(s) of the electromagnetic waves for any of theforegoing embodiments can be fundamental mode(s), non-fundamentalmode(s), or combinations thereof.

FIG. 18B is a block diagram illustrating an example, non-limitingembodiment of bundled transmission media 1836 in accordance with variousaspects described herein. The bundled transmission media 1836 cancomprise a plurality of cables 1838 held in place by a flexible sleeve1839. The plurality of cables 1838 can comprise multiple instances ofcable 1800 of FIG. 18A. The sleeve 1839 can comprise a dielectricmaterial that prevents soil, water or other external materials frommaking contact with the plurality of cables 1838. In an embodiment, aplurality of launchers, each utilizing a transceiver similar to the onedepicted in FIG. 10 or other coupling devices described herein, can beadapted to selectively induce a guided electromagnetic wave in eachcable, each guided electromagnetic wave conveys different data (e.g.,voice, video, messaging, content, etc.). In an embodiment, by adjustingoperational parameters of each launcher or other coupling device, theelectric field intensity profile of each guided electromagnetic wave canbe fully or substantially confined within layers of a correspondingcable 1838 to reduce cross-talk between cables 1838.

In situations where the electric field intensity profile of each guidedelectromagnetic wave is not fully or substantially confined within acorresponding cable 1838, cross-talk of electromagnetic signals canoccur between cables 1838. Several mitigation options can be used toreduce cross-talk between the cables 1838 of FIG. 18B. In an embodiment,an absorption material 1840 that can absorb electromagnetic fields, suchas carbon, can be applied to the cables 1838 as shown in FIG. 18B topolarize each guided electromagnetic wave at various polarization statesto reduce cross-talk between cables 1838. In another embodiment (notshown), carbon beads can be added to gaps between the cables 1838 toreduce cross-talk.

In yet another embodiment (not shown), a diameter of cable 1838 can beconfigured differently to vary a speed of propagation of guidedelectromagnetic waves between the cables 1838 in order to reducecross-talk between cables 1838. In an embodiment (not shown), a shape ofeach cable 1838 can be made asymmetric (e.g., elliptical) to direct theguided electromagnetic fields of each cable 1838 away from each other toreduce cross-talk. In an embodiment (not shown), a filler material suchas dielectric foam can be added between cables 1838 to sufficientlyseparate the cables 1838 to reduce cross-talk therebetween. In anembodiment (not shown), longitudinal carbon strips or swirls can beapplied to on an outer surface of the jacket 1806 of each cable 1838 toreduce radiation of guided electromagnetic waves outside of the jacket1806 and thereby reduce cross-talk between cables 1838. In yet anotherembodiment, each launcher can be configured to launch a guidedelectromagnetic wave having a different frequency, modulation, wavepropagation mode, such as an orthogonal frequency, modulation or mode,to reduce cross-talk between the cables 1838.

In yet another embodiment (not shown), pairs of cables 1838 can betwisted in a helix to reduce cross-talk between the pairs and othercables 1838 in a vicinity of the pairs. In some embodiments, certaincables 1838 can be twisted while other cables 1838 are not twisted toreduce cross-talk between the cables 1838. Additionally, each twistedpair cable 1838 can have different pitches (i.e., different twist rates,such as twists per meter) to further reduce cross-talk between the pairsand other cables 1838 in a vicinity of the pairs. In another embodiment(not shown), launchers or other coupling devices can be configured toinduce guided electromagnetic waves in the cables 1838 havingelectromagnetic fields that extend beyond the jacket 1806 into gapsbetween the cables to reduce cross-talk between the cables 1838. It issubmitted that any one of the foregoing embodiments for mitigatingcross-talk between cables 1838 can be combined to further reducecross-talk therebetween.

Turning now to FIG. 18C, a block diagram illustrating an example,non-limiting embodiment of exposed tapered stubs from the bundledtransmission media 1836 for use as antennas 1855 is shown. Each antenna1855 can serve as a directional antenna for radiating wireless signalsdirected to wireless communication devices or for inducingelectromagnetic wave propagation on a surface of a transmission medium(e.g., a power line). In an embodiment, the wireless signals radiated bythe antennas 1855 can be beam steered by adapting the phase and/or othercharacteristics of the wireless signals generated by each antenna 1855.In an embodiment, the antennas 1855 can individually be placed in apie-pan antenna assembly for directing wireless signals in variousdirections.

It is further noted that the terms “core”, “cladding”, “shell”, and“foam” as utilized in the subject disclosure can comprise any types ofmaterials (or combinations of materials) that enable electromagneticwaves to remain bound to the core while propagating longitudinally alongthe core. For example, a strip of dielectric foam 1804″ describedearlier can be replaced with a strip of an ordinary dielectric material(e.g., polyethylene) for wrapping around the dielectric core 1802(referred to herein for illustration purposes only as a “wrap”). In thisconfiguration an average density of the wrap can be small as a result ofair space between sections of the wrap. Consequently, an effectivedielectric constant of the wrap can be less than the dielectric constantof the dielectric core 1802, thereby enabling guided electromagneticwaves to remain bound to the core. Accordingly, any of the embodimentsof the subject disclosure relating to materials used for core(s) andwrappings about the core(s) can be structurally adapted and/or modifiedwith other dielectric materials that achieve the result of maintainingelectromagnetic waves bound to the core(s) while they propagate alongthe core(s). Additionally, a core in whole or in part as described inany of the embodiments of the subject disclosure can comprise an opaquematerial (e.g., polyethylene) that is resistant to propagation ofelectromagnetic waves having an optical operating frequency.

Accordingly, electromagnetic waves guided and bound to the core willhave a non-optical frequency range (e.g., less than the lowest frequencyof visible light).

FIGS. 18D, 18E, 18F, 18G, 18H, and 18I and 18J are block diagramsillustrating example, non-limiting embodiments of a waveguide device fortransmitting or receiving electromagnetic waves in accordance withvarious aspects described herein. In an embodiment, FIG. 18D illustratesa front view of a waveguide device 1865 having a plurality of slots 1863(e.g., openings or apertures) for emitting electromagnetic waves havingradiated electric fields (e-fields) 1861. In an embodiment, the radiatede-fields 1861 of pairs of symmetrically positioned slots 1863 (e.g.,north and south slots of the waveguide 1865) can be directed away fromeach other (i.e., polar opposite radial orientations about the cable1862). While the slots 1863 are shown as having a rectangular shape,other shapes such as other polygons, sector and arc shapes, ellipsoidshapes and other shapes are likewise possible. For illustration purposesonly, the term north will refer to a relative azimuthaldirection/orientation as shown in the figures. All references in thesubject disclosure to other directions/orientations (e.g., south, east,west, northwest, and so forth) will be relative to northernillustration. In an embodiment, to achieve e-fields with opposingorientations at the north and south slots 1863, for example, the northand south slots 1863 can be arranged to have a circumferential distancebetween each other that is approximately one wavelength ofelectromagnetic waves signals supplied to these slots. The waveguide1865 can have a cylindrical cavity in a center of the waveguide 1865 toenable placement of a cable 1862. In one embodiment, the cable 1862 cancomprise an insulated conductor. In another embodiment, the cable 1862can comprise an uninsulated conductor. In yet other embodiments, thecable 1862 can comprise any of the embodiments of a transmission core1852 of cable 1850 previously described.

In one embodiment, the cable 1862 can slide into the cylindrical cavityof the waveguide 1865. In another embodiment, the waveguide 1865 canutilize an assembly mechanism (not shown). The assembly mechanism (e.g.,a hinge or other suitable mechanism that provides a way to open thewaveguide 1865 at one or more locations) can be used to enable placementof the waveguide 1865 on an outer surface of the cable 1862 or otherwiseto assemble separate pieces together to form the waveguide 1865 asshown. According to these and other suitable embodiments, the waveguide1865 can be configured to wrap around the cable 1862 like a collar.

FIG. 18E illustrates a side view of an embodiment of the waveguide 1865.The waveguide 1865 can be adapted to have a hollow rectangular waveguideportion 1867 that receives electromagnetic waves 1866 generated by atransmitter circuit as previously described in the subject disclosure(e.g., see FIGS. 1 and 10). The electromagnetic waves 1866 can bedistributed by the hollow rectangular waveguide portion 1867 into in ahollow collar 1869 of the waveguide 1865. The rectangular waveguideportion 1867 and the hollow collar 1869 can be constructed of materialssuitable for maintaining the electromagnetic waves within the hollowchambers of these assemblies (e.g., carbon fiber materials). It shouldbe noted that while the waveguide portion 1867 is shown and described ina hollow rectangular configuration, other shapes and/or other non-hollowconfigurations can be employed. In particular, the waveguide portion1867 can have a square or other polygonal cross section, an arc orsector cross section that is truncated to conform to the outer surfaceof the cable 1862, a circular or ellipsoid cross section or crosssectional shape. In addition, the waveguide portion 1867 can beconfigured as, or otherwise include, a solid dielectric material.

As previously described, the hollow collar 1869 can be configured toemit electromagnetic waves from each slot 1863 with opposite e-fields1861 at pairs of symmetrically positioned slots 1863 and 1863′. In anembodiment, the electromagnetic waves emitted by the combination ofslots 1863 and 1863′ can in turn induce electromagnetic waves 1868 onthat are bound to the cable 1862 for propagation according to afundamental wave mode without other wave modes present—such asnon-fundamental wave modes. In this configuration, the electromagneticwaves 1868 can propagate longitudinally along the cable 1862 to otherdownstream waveguide systems coupled to the cable 1862.

It should be noted that since the hollow rectangular waveguide portion1867 of FIG. 18E is closer to slot 1863 (at the northern position of thewaveguide 1865), slot 1863 can emit electromagnetic waves having astronger magnitude than electromagnetic waves emitted by slot 1863′ (atthe southern position). To reduce magnitude differences between theseslots, slot 1863′ can be made larger than slot 1863. The technique ofutilizing different slot sizes to balance signal magnitudes betweenslots can be applied to any of the embodiments of the subject disclosurerelating to FIGS. 18D, 18E, 18G, and 18I—some of which are describedbelow.

In another embodiment, FIG. 18F depicts a waveguide 1865′ that can beconfigured to utilize circuitry such as monolithic microwave integratedcircuits (MMICs) 1870 each coupled to a signal input 1872 (e.g., coaxialcable that provides a communication signal). The signal input 1872 canbe generated by a transmitter circuit as previously described in thesubject disclosure (e.g., see reference 101, 1000 of FIGS. 1 and 10)adapted to provide electrical signals to the MMICs 1870. Each MMIC 1870can be configured to receive signal 1872 which the MMIC 1870 canmodulate and transmit with a radiating element (e.g., an antenna) toemit electromagnetic waves having radiated e-fields 1861. In oneembodiment, the MMICs 1870 can be configured to receive the same signal1872, but transmit electromagnetic waves having e-fields 1861 ofopposing orientation. This can be accomplished by configuring one of theMMICs 1870 to transmit electromagnetic waves that are 180 degrees out ofphase with the electromagnetic waves transmitted by the other MMIC 1870.In an embodiment, the combination of the electromagnetic waves emittedby the MMICs 1870 can together induce electromagnetic waves 1868 thatare bound to the cable 1862 for propagation according to a fundamentalwave mode without other wave modes present—such as non-fundamental wavemodes. In this configuration, the electromagnetic waves 1868 canpropagate longitudinally along the cable 1862 to other downstreamwaveguide systems coupled to the cable 1862.

A tapered horn 1880 can be added to the embodiments of FIGS. 18E and 18Fto assist in the inducement of the electromagnetic waves 1868 on cable1862 as depicted in FIGS. 18G and 18H. In an embodiment where the cable1862 is an uninsulated conductor, the electromagnetic waves induced onthe cable 1862 can have a large radial dimension (e.g., 1 meter). Toenable use of a smaller tapered horn 1880, an insulation layer 1879 canbe applied on a portion of the cable 1862 at or near the cavity asdepicted with hash lines in FIGS. 18G and 18H. The insulation layer 1879can have a tapered end facing away from the waveguide 1865. The addedinsulation enables the electromagnetic waves 1868 initially launched bythe waveguide 1865 (or 1865′) to be tightly bound to the insulation,which in turn reduces the radial dimension of the electromagnetic fields1868 (e.g., centimeters). As the electromagnetic waves 1868 propagateaway from the waveguide 1865 (1865′) and reach the tapered end of theinsulation layer 1879, the radial dimension of the electromagnetic waves1868 begin to increase eventually achieving the radial dimension theywould have had had the electromagnetic waves 1868 been induced on theuninsulated conductor without an insulation layer. In the illustrationof FIGS. 18G and 18H the tapered end begins at an end of the taperedhorn 1880. In other embodiments, the tapered end of the insulation layer1879 can begin before or after the end of the tapered horn 1880. Thetapered horn can be metallic or constructed of other conductive materialor constructed of a plastic or other non-conductive material that iscoated or clad with a dielectric layer or doped with a conductivematerial to provide reflective properties similar to a metallic horn.

In an embodiment, cable 1862 can comprise any of the embodiments ofcable 1850 described earlier. In this embodiment, waveguides 1865 and1865′ can be coupled to a transmission core 1852 of cable 1850 asdepicted in FIGS. 18I and 18J. The waveguides 1865 and 1865′ can induce,as previously described, electromagnetic waves 1868 on the transmissioncore 1852 for propagation entirely or partially within inner layers ofcable 1850.

It is noted that for the foregoing embodiments of FIGS. 18G, 18H, 18Iand 18J, electromagnetic waves 1868 can be bidirectional. For example,electromagnetic waves 1868 of a different operating frequency can bereceived by slots 1863 or MMICs 1870 of the waveguides 1865 and 1865′,respectively. Once received, the electromagnetic waves can be convertedby a receiver circuit (e.g., see reference 101, 1000 of FIGS. 1 and 10)for generating a communication signal for processing.

Although not shown, it is further noted that the waveguides 1865 and1865′ can be adapted so that the waveguides 1865 and 1865′ can directelectromagnetic waves 1868 upstream or downstream longitudinally. Forexample, a first tapered horn 1880 coupled to a first instance of awaveguide 1865 or 1865′ can be directed westerly on cable 1862, while asecond tapered horn 1880 coupled to a second instance of a waveguide1865 or 1865′ can be directed easterly on cable 1862. The first andsecond instances of the waveguides 1865 or 1865′ can be coupled so thatin a repeater configuration, signals received by the first waveguide1865 or 1865′ can be provided to the second waveguide 1865 or 1865′ forretransmission in an easterly direction on cable 1862. The repeaterconfiguration just described can also be applied from an easterly towesterly direction on cable 1862.

In another embodiment, the waveguide 1865′ of FIGS. 18G, 18H, 18I and18J can also be configured to generate electromagnetic waves havingnon-fundamental wave modes. This can be accomplished by adding moreMMICs 1870 as depicted in FIG. 18K. Each MMIC 1870 can be configured toreceive the same signal input 1872. However, MMICs 1870 can selectivelybe configured to emit electromagnetic waves having differing phasesusing controllable phase-shifting circuitry in each MMIC 1870. Forexample, the northerly and southerly MMICs 1870 can be configured toemit electromagnetic waves having a 180 degree phase difference, therebyaligning the e-fields either in a northerly or southerly direction. Anycombination of pairs of MMICs 1870 (e.g., westerly and easterly MMICs1870, northwesterly and southeasterly MMICs 1870, northeasterly andsouthwesterly MMICs 1870) can be configured with opposing or alignede-fields. Consequently, waveguide 1865′ can be configured to generateelectromagnetic waves with one or more non-fundamental wave modes suchas TMnm, HEnm or EHnm modes where n and m are non-negative integers andeither n or m is non-zero, electromagnetic waves with one or morefundamental wave modes such as TM00, or any combinations thereof.

It is submitted that it is not necessary to select slots 1863 in pairsto generate electromagnetic waves having a non-fundamental wave mode.For example, electromagnetic waves having a non-fundamental wave modecan be generated by enabling a single slot from a plurality of slots anddisabling all other slots. In particular, a single MMIC 1870 of theMMICs 1870 shown in FIG. 18K can be configured to generateelectromagnetic waves having a non-fundamental wave mode while all otherMMICs 1870 are not in use or disabled. Likewise, other wave modes andwave mode combinations can be induced by enabling other non-null propersubsets of waveguide slots 1863 or the MMICs 1870.

It is further noted that in some embodiments, the waveguide systems 1865and 1865′ may generate combinations of fundamental and non-fundamentalwave modes where one wave mode is dominant over the other. For example,in one embodiment electromagnetic waves generated by the waveguidesystems 1865 and 1865′ may have a weak signal component that has anon-fundamental wave mode, and a substantially strong signal componentthat has a fundamental wave mode. Accordingly, in this embodiment, theelectromagnetic waves have a substantially fundamental wave mode. Inanother embodiment electromagnetic waves generated by the waveguidesystems 1865 and 1865′ may have a weak signal component that has afundamental wave mode, and a substantially strong signal component thathas a non-fundamental wave mode. Accordingly, in this embodiment, theelectromagnetic waves have a substantially non-fundamental wave mode.Further, a non-dominant wave mode may be generated that propagates onlytrivial distances along the length of the transmission medium.

It is also noted that the waveguide systems 1865 and 1865′ can beconfigured to generate instances of electromagnetic waves that have wavemodes that can differ from a resulting wave mode or modes of thecombined electromagnetic wave. It is further noted that each MMIC 1870of the waveguide system 1865′ of FIG. 18K can be configured to generatean instance of electromagnetic waves having wave characteristics thatdiffer from the wave characteristics of another instance ofelectromagnetic waves generated by another MMIC 1870. One MMIC 1870, forexample, can generate an instance of an electromagnetic wave having aspatial orientation and a phase, frequency, magnitude, electric fieldorientation, and/or magnetic field orientation that differs from thespatial orientation and phase, frequency, magnitude, electric fieldorientation, and/or magnetic field orientation of a different instanceof another electromagnetic wave generated by another MMIC 1870. Thewaveguide system 1865′ can thus be configured to generate instances ofelectromagnetic waves having different wave and spatial characteristics,which when combined achieve resulting electromagnetic waves having oneor more desirable wave modes.

From these illustrations, it is submitted that the waveguide systems1865 and 1865′ can be adapted to generate electromagnetic waves with oneor more selectable wave modes. In one embodiment, for example, thewaveguide systems 1865 and 1865′ can be adapted to select one or morewave modes and generate electromagnetic waves having a single wave modeor multiple wave modes selected and produced from a process of combininginstances of electromagnetic waves having one or more configurable waveand spatial characteristics. In an embodiment, for example, parametricinformation can be stored in a look-up table. Each entry in the look-uptable can represent a selectable wave mode. A selectable wave mode canrepresent a single wave mode, or a combination of wave modes. Thecombination of wave modes can have one or dominant wave modes. Theparametric information can provide configuration information forgenerating instances of electromagnetic waves for producing resultantelectromagnetic waves that have the desired wave mode.

For example, once a wave mode or modes is selected, the parametricinformation obtained from the look-up table from the entry associatedwith the selected wave mode(s) can be used to identify which of one ormore MMICs 1870 to utilize, and/or their corresponding configurations toachieve electromagnetic waves having the desired wave mode(s). Theparametric information may identify the selection of the one or moreMMICs 1870 based on the spatial orientations of the MMICs 1870, whichmay be required for producing electromagnetic waves with the desiredwave mode. The parametric information can also provide information toconfigure each of the one or more MMICs 1870 with a particular phase,frequency, magnitude, electric field orientation, and/or magnetic fieldorientation which may or may not be the same for each of the selectedMMICs 1870. A look-up table with selectable wave modes and correspondingparametric information can be adapted for configuring the slottedwaveguide system 1865.

In some embodiments, a guided electromagnetic wave can be considered tohave a desired wave mode if the corresponding wave mode propagatesnon-trivial distances on a transmission medium and has a field strengththat is substantially greater in magnitude (e.g., 20 dB higher inmagnitude) than other wave modes that may or may not be desirable. Sucha desired wave mode or modes can be referred to as dominant wave mode(s)with the other wave modes being referred to as non-dominant wave modes.In a similar fashion, a guided electromagnetic wave that is said to besubstantially without the fundamental wave mode has either nofundamental wave mode or a non-dominant fundamental wave mode. A guidedelectromagnetic wave that is said to be substantially without anon-fundamental wave mode has either no non-fundamental wave mode(s) oronly non-dominant non-fundamental wave mode(s). In some embodiments, aguided electromagnetic wave that is said to have only a single wave modeor a selected wave mode may have only one corresponding dominant wavemode.

Turning now to FIGS. 19A and 19B, block diagrams illustrating example,non-limiting embodiments of a dielectric antenna and corresponding gainand field intensity plots in accordance with various aspects describedherein are shown. FIG. 19A depicts a dielectric horn antenna 1901 havinga conical structure. The dielectric horn antenna 1901 is coupled to oneend 1902′ of a feedline 1902 having a feed point 1902″ at an oppositeend of the feedline 1902. The dielectric horn antenna 1901 and thefeedline 1902 (as well as other embodiments of the dielectric antennadescribed below in the subject disclosure) can be constructed ofdielectric materials such as a polyethylene material, a polyurethanematerial or other suitable dielectric material (e.g., a synthetic resin,other plastics, etc.). The dielectric horn antenna 1901 and the feedline1902 (as well as other embodiments of the dielectric antenna describedbelow in the subject disclosure) can be conductorless and/or besubstantially or entirely devoid of any conductive materials.

For example, the external surfaces 1907 of the dielectric horn antenna1901 and the feedline 1902 can be non-conductive or substantiallynon-conductive with at least 95% of the external surface area beingnon-conductive and the dielectric materials used to construct thedielectric horn antenna 1901 and the feedline 1902 can be such that theysubstantially do not contain impurities that may be conductive (e.g.,such as less than 1 part per thousand) or result in imparting conductiveproperties. In other embodiments, however, a limited number ofconductive components can be used such as a metallic connector componentused for coupling to the feed point 1902″ of the feedline 1902 with oneor more screws, rivets or other coupling elements used to bindcomponents to one another, and/or one or more structural elements thatdo not significantly alter the radiation pattern of the dielectricantenna.

The feed point 1902″ can be adapted to couple to a core 1852 such ascore 1802 previously described by way of illustration in FIG. 18A. Inone embodiment, the feed point 1902″ can be coupled to the core 1852utilizing a joint (not shown in FIG. 19A). Other embodiments forcoupling the feed point 1902″ to the core 1852 can be used. In anembodiment, the joint can be configured to cause the feed point 1902″ totouch an endpoint of the core 1852. In another embodiment, the joint cancreate a gap between the feed point 1902″ and an end of the core 1852.In yet another embodiment, the joint can cause the feed point 1902″ andthe core 1852 to be coaxially aligned or partially misaligned.Notwithstanding any combination of the foregoing embodiments,electromagnetic waves can in whole or at least in part propagate betweenthe junction of the feed point 1902″ and the core 1852.

The cable 1850 can be coupled to the waveguide system 1865 or thewaveguide system 1865′. For illustration purposes only, reference willbe made to the waveguide system 1865′. It is understood, however, thatthe waveguide system 1865 or other waveguide systems can also beutilized in accordance with the discussions that follow. The waveguidesystem 1865′ can be configured to select a wave mode (e.g.,non-fundamental wave mode, fundamental wave mode, a hybrid wave mode, orcombinations thereof as described earlier) and transmit instances ofelectromagnetic waves having a non-optical operating frequency (e.g., 60GHz). The electromagnetic waves can be directed to an interface of thecable 1850.

The instances of electromagnetic waves generated by the waveguide system1865′ can induce a combined electromagnetic wave having the selectedwave mode that propagates from the core 1852 to the feed point 1902″.The combined electromagnetic wave can propagate partly inside the core1852 and partly on an outer surface of the core 1852. Once the combinedelectromagnetic wave has propagated through the junction between thecore 1852 and the feed point 1902″, the combined electromagnetic wavecan continue to propagate partly inside the feedline 1902 and partly onan outer surface of the feedline 1902. In some embodiments, the portionof the combined electromagnetic wave that propagates on the outersurface of the core 1852 and the feedline 1902 is small. In theseembodiments, the combined electromagnetic wave can be said to be guidedby and tightly coupled to the core 1852 and the feedline 1902 whilepropagating longitudinally towards the dielectric antenna 1901.

When the combined electromagnetic wave reaches a proximal portion of thedielectric antenna 1901 (at a junction 1902′ between the feedline 1902and the dielectric antenna 1901), the combined electromagnetic waveenters the proximal portion of the dielectric antenna 1901 andpropagates longitudinally along an axis of the dielectric antenna 1901(shown as a hashed line). By the time the combined electromagnetic wavereaches the aperture 1903, the combined electromagnetic wave has anintensity pattern similar to the one shown by the side view and frontview depicted in FIG. 19B. The electric field intensity pattern of FIG.19B shows that the electric fields of the combined electromagnetic wavesare strongest in a center region of the aperture 1903 and weaker in theouter regions. In an embodiment, where the wave mode of theelectromagnetic waves propagating in the dielectric antenna 1901 is ahybrid wave mode (e.g., HE11), the leakage of the electromagnetic wavesat the external surfaces 1907 is reduced or in some instanceseliminated. It is further noted that while the dielectric antenna 1901is constructed of a solid dielectric material having no physicalopening, the front or operating face of the dielectric antenna 1901 fromwhich free space wireless signals are radiated or received will bereferred to as the aperture 1903 of the dielectric antenna 1901 eventhough in some prior art systems the term aperture may be used todescribe an opening of an antenna that radiates or receives free spacewireless signals. Methods for launching a hybrid wave mode on cable 1850is discussed below.

In an embodiment, the far-field antenna gain pattern depicted in FIG.19B can be widened by decreasing the operating frequency of the combinedelectromagnetic wave from a nominal frequency. Similarly, the gainpattern can be narrowed by increasing the operating frequency of thecombined electromagnetic wave from the nominal frequency. Accordingly, awidth of a beam of wireless signals emitted by the aperture 1903 can becontrolled by configuring the waveguide system 1865′ to increase ordecrease the operating frequency of the combined electromagnetic wave.

The dielectric antenna 1901 of FIG. 19A can also be used for receivingwireless signals, such as free space wireless signals transmitted byeither a similar antenna or conventional antenna design. Wirelesssignals received by the dielectric antenna 1901 at the aperture 1903induce electromagnetic waves in the dielectric antenna 1901 thatpropagate towards the feedline 1902. The electromagnetic waves continueto propagate from the feedline 1902 to the junction between the feedpoint 1902″ and an endpoint of the core 1852, and are thereby deliveredto the waveguide system 1865′ coupled to the cable 1850. In thisconfiguration, the waveguide system 1865′ can perform bidirectionalcommunications utilizing the dielectric antenna 1901. It is furthernoted that in some embodiments the core 1852 of the cable 1850 (shownwith dashed lines) can be configured to be collinear with the feed point1902″ to avoid a bend shown in FIG. 19A. In some embodiments, acollinear configuration can reduce an alteration in the propagation ofthe electromagnetic due to the bend in cable 1850.

Turning now to FIG. 19C, a block diagram is shown illustrating anexample, non-limiting embodiment of a dielectric antenna 1901 coupled toor integrally constructed with a lens 1912 in accordance with variousaspects described herein. In one embodiment, the lens 1912 can comprisea dielectric material having a first dielectric constant that issubstantially similar or equal to a second dielectric constant of thedielectric antenna 1901. In other embodiments, the lens 1912 cancomprise a dielectric material having a first dielectric constant thatdiffers from a second dielectric constant of the dielectric antenna1901. In either of these embodiments, the shape of the lens 1912 can bechosen or formed so as to equalize the delays of the variouselectromagnetic waves propagating at different points in the dielectricantenna 1901. In one embodiment, the lens 1912 can be an integral partof the dielectric antenna 1901 as depicted in the top diagram of FIG.19C and in particular, the lens and dielectric antenna 1901 can bemolded, machined or otherwise formed from a single piece of dielectricmaterial. Alternatively, the lens 1912 can be an assembly component ofthe dielectric antenna 1901 as depicted in the bottom diagram of FIG.19C, which can be attached by way of an adhesive material, brackets onthe outer edges, or other suitable attachment techniques. The lens 1912can have a convex structure as shown in FIG. 19C which is adapted toadjust a propagation of electromagnetic waves in the dielectric antenna1901. While a round lens and conical dielectric antenna configuration isshown, other shapes include pyramidal shapes, elliptical shapes andother geometric shapes can likewise be implemented.

In particular, the curvature of the lens 1912 can be chosen in mannerthat reduces phase differences between near-field wireless signalsgenerated by the aperture 1903 of the dielectric antenna 1901. The lens1912 accomplishes this by applying location-dependent delays topropagating electromagnetic waves. Because of the curvature of the lens1912, the delays differ depending on where the electromagnetic wavesemanate from at the aperture 1903. For example, electromagnetic wavespropagating by way of a center axis 1905 of the dielectric antenna 1901will experience more delay through the lens 1912 than electromagneticwaves propagating radially away from the center axis 1905.Electromagnetic waves propagating towards, for example, the outer edgesof the aperture 1903 will experience minimal or no delay through thelens. Propagation delay increases as the electromagnetic waves get closeto the center axis 1905. Accordingly, a curvature of the lens 1912 canbe configured so that near-field wireless signals have substantiallysimilar phases. By reducing differences between phases of the near-fieldwireless signals, a width of far-field signals generated by thedielectric antenna 1901 is reduced, which in turn increases theintensity of the far-field wireless signals within the width of the mainlobe, producing a relatively narrow beam pattern with high gain.

It should be noted that the lens 1912 can be configured in other lensconfigurations. For example, the lens 1912 can comprise concentricridges 1914 configured to have a depth representative of a selectwavelength factor. For example, a ridge can be configured to have adepth of one-quarter a wavelength of the electromagnetic wavespropagating in the dielectric antenna 1901. Such a configuration causesthe electromagnetic wave reflected from one ridge to have a phasedifference of 180 degrees relative to the electromagnetic wave reflectedfrom an adjacent ridge. Consequently, the out of phase electromagneticwaves reflected from the adjacent risers 1916 substantially cancel,thereby reducing reflection and distortion caused thereby.

Turning now to FIG. 19D, a block diagram illustrating an example,non-limiting embodiment of near-field signals 1928 and far-field signals1930 emitted by the dielectric antenna 1901 having an ellipticalaperture in accordance with various aspects described herein is shown.The cross section of the near-field beam pattern 1928 mimics theelliptical shape of the aperture 1903 of the dielectric antenna 1901.The cross section of the far-field beam pattern 1930 have a rotationaloffset (approximately 90 degrees) that results from the elliptical shapeof the near-field signals 1928. The offset can be determined by applyinga Fourier Transform to the near-field signals 1928. While the crosssection of the near-field beam pattern 1928 and the cross section of thefar-field beam pattern 1930 are shown as nearly the same size in orderto demonstrate the rotational effect, the actual size of the far-fieldbeam pattern 1930 may increase with the distance from the dielectricantenna 1901.

The elongated shape of the far-field signals 1930 and its orientationcan prove useful when aligning a dielectric antenna 1901 in relation toa remotely located receiver configured to receive the far-field signals1930. The receiver can comprise one or more dielectric antennas coupledto a waveguide system such as described by the subject disclosure. Theelongated far-field signals 1930 can increase the likelihood that theremotely located receiver will detect the far-field signals 1930. Inaddition, the elongated far-field signals 1930 can be useful insituations where a dielectric antenna 1901 coupled to a gimbal assembly,or other actuated antenna mount (not shown) In particular, the elongatedfar-field signals 1930 can be useful in situations where such as gimbalmount only has two degrees of freedom for aligning the dielectricantenna 1901 in the direction of the receiver (e.g., yaw and pitch isadjustable but roll is fixed).

Although not shown, it will be appreciated that the dielectric antenna1901 can have an integrated or attachable lens 1912 as previouslydescribed to increase an intensity of the far-fields signals 1930 byreducing phase differences in the near-field signals.

Turning now to FIG. 19E, a block diagram of an example, non-limitingembodiment of a dielectric antenna 1901′ in accordance with variousaspects described herein is shown. FIG. 19E depicts an array ofpyramidal-shaped dielectric horn antennas 1901′, each having acorresponding aperture 1903′. Each antenna of the array ofpyramidal-shaped dielectric horn antennas 1901′ can have a feedline 1902with a corresponding feed point 1902″ that couples to each correspondingcore 1852 of a plurality of cables 1850. Each cable 1850 can be coupledto a different (or a same) waveguide system 1865′. The array ofpyramidal-shaped dielectric horn antennas 1901′ can be used to transmitwireless signals having a plurality of spatial orientations. An array ofpyramidal-shaped dielectric horn antennas 1901′ covering 360 degrees canenable a one or more waveguide systems 1865′ coupled to the antennas toperform omnidirectional communications with other communication devicesor antennas of similar type.

The bidirectional propagation properties of electromagnetic wavespreviously described for the dielectric antenna 1901 of FIG. 19A arealso applicable for electromagnetic waves propagating from the core 1852to the feed point 1902″ guided by the feedline 1902 to the aperture1903′ of the pyramidal-shaped dielectric horn antennas 1901′, and in thereverse direction. Similarly, the array of pyramidal-shaped dielectrichorn antennas 1901′ can be substantially or entirely devoid ofconductive external surfaces and internal conductive materials asdiscussed above. For example, in some embodiments, the array ofpyramidal-shaped dielectric horn antennas 1901′ and their correspondingfeed points 1902′ can be constructed of dielectric-only materials suchas polyethylene or polyurethane materials or with only trivial amountsof conductive material that does not significantly alter the radiationpattern of the antenna.

It is further noted that each antenna of the array of pyramidal-shapeddielectric horn antennas 1901′ can have similar gain and electric fieldintensity maps as shown for the dielectric antenna 1901 in FIG. 19B.Each antenna of the array of pyramidal-shaped dielectric horn antennas1901′ can also be used for receiving wireless signals as previouslydescribed for the dielectric antenna 1901 of FIG. 19A. In someembodiments, a single instance of a pyramidal-shaped dielectric hornantenna can be used. Similarly, multiple instances of the dielectricantenna 1901 of FIG. 19A can be used in an array configuration similarto the one shown in FIG. 19E.

Turning now to FIG. 19F, block diagrams of example, non-limitingembodiments of an array 1976 of dielectric antennas 1901 configurablefor steering wireless signals in accordance with various aspectsdescribed herein is shown. The array 1976 of dielectric antennas 1901can be conical shaped antennas 1901 or pyramidal-shaped dielectricantennas 1901′. To perform beam steering, a waveguide system coupled tothe array 1976 of dielectric antennas 1901 can be adapted to utilize acircuit 1972 comprising amplifiers 1973 and phase shifters 1974, eachpair coupled to one of the dielectric antennas 1901 in the array 1976.The waveguide system can steer far-field wireless signals from left toright (west to east) by incrementally increasing a phase delay ofsignals supplied to the dielectric antennas 1901.

For example, the waveguide system can provide a first signal to thedielectric antennas of column 1 (“C1”) having no phase delay. Thewaveguide system can further provide a second signal to column 2 (“C2”),the second signal comprising the first signal having a first phasedelay. The waveguide system can further provide a third signal to thedielectric antennas of column 3 (“C3”), the third signal comprising thesecond signal having a second phase delay. Lastly, the waveguide systemcan provide a fourth signal to the dielectric antennas of column 4(“C4”), the fourth signal comprising the third signal having a thirdphase delay. These phase shifted signals will cause far-field wirelesssignals generated by the array to shift from left to right. Similarly,far-field signals can be steered from right to left (east to west) (“C4”to “C1”), north to south (“R1” to “R4”), south to north (“R4” to “R1”),and southwest to northeast (“C1-R4” to “C4-R1”).

Utilizing similar techniques beam steering can also be performed inother directions such as southwest to northeast by configuring thewaveguide system to incrementally increase the phase of signalstransmitted by the following sequence of antennas: “C1-R4”,“C1-R3/C2-R4”, “C1-R2/C2-R3/C3-R4”, “C1-R1/C2-R2/C3- R3/C4-R4”,“C2-R1/C3-R2/C4-R3”, “C3-R1/C4-R2”, “C4-R1”. In a similar way, beamsteering can be performed northeast to southwest, northwest tosoutheast, southeast to northwest, as well in other directions inthree-dimensional space. Beam steering can be used, among other things,for aligning the array 1976 of dielectric antennas 1901 with a remotereceiver and/or for directivity of signals to mobile communicationdevices. In some embodiments, a phased array 1976 of dielectric antennas1901 can also be used to circumvent the use of the gimbal assembly ofFIG. 19M or other actuated mount. While the foregoing has described beamsteering controlled by phase delays, gain and phase adjustment canlikewise be applied to the dielectric antennas 1901 of the phased array1976 in a similar fashion to provide additional control and versatilityin the formation of a desired beam pattern.

Turning now to FIGS. 20A and 20B, block diagrams illustrating example,non-limiting embodiments of the cable 1850 of FIG. 18A used for inducingguided electromagnetic waves on power lines supported by utility poles.In one embodiment, as depicted in FIG. 20A, a cable 1850 can be coupledat one end to a microwave apparatus that launches guided electromagneticwaves within one or more inner layers of cable 1850 utilizing, forexample, the hollow waveguide 1808 shown in FIG. 18A. The microwaveapparatus can utilize a microwave transceiver such as shown in FIG. 10for transmitting or receiving signals from cable 1850. The guidedelectromagnetic waves induced in the one or more inner layers of cable1850 can propagate to an exposed stub of the cable 1850 located inside ahorn antenna (shown as a dotted line in FIG. 20A) for radiating theelectromagnetic waves via the horn antenna. The radiated signals fromthe horn antenna in turn can induce guided electromagnetic waves thatpropagate longitudinally on power line such as a medium voltage (MV)power line. In one embodiment, the microwave apparatus can receive ACpower from a low voltage (e.g., 220V) power line. Alternatively, thehorn antenna can be replaced with a stub antenna as shown in FIG. 20B toinduce guided electromagnetic waves that propagate longitudinally on apower line such as the MV power line or to transmit wireless signals toother antenna system(s).

In an alternative embodiment, the hollow horn antenna shown in FIG. 20Acan be replaced with a solid dielectric antenna such as the dielectricantenna 1901 of FIG. 19A, or the pyramidal-shaped horn antenna 1901′ ofFIG. 19E. In this embodiment the horn antenna can radiate wirelesssignals directed to another horn antenna such as the bidirectional hornantennas 2040 shown in FIG. 20C. In this embodiment, each horn antenna2040 can transmit wireless signals to another horn antenna 2040 orreceive wireless signals from the other horn antenna 2040 as shown inFIG. 20C. Such an arrangement can be used for performing bidirectionalwireless communications between antennas. Although not shown, the hornantennas 2040 can be configured with an electromechanical device tosteer a direction of the horn antennas 2040.

In alternate embodiments, first and second cables 1850A′ and 1850B′ canbe coupled to the microwave apparatus and to a transformer 2052,respectively, as shown in FIGS. 20A and 20B. The first and second cables1850A′ and 1850B′ can be represented by, for example, cable 1800 eachmodified to have a conductive core. A first end of the conductive coreof the first cable 1850A′ can be coupled to the microwave apparatus forpropagating guided electromagnetic waves launched therein. A second endof the conductive core of the first cable 1850A′ can be coupled to afirst end of a conductive coil of the transformer 2052 for receiving theguided electromagnetic waves propagating in the first cable 1850A′ andfor supplying signals associated therewith to a first end of a secondcable 1850B′ by way of a second end of the conductive coil of thetransformer 2052. A second end of the second cable 1850B′ can be coupledto the horn antenna of FIG. 20A or can be exposed as a stub antenna ofFIG. 20B for inducing guided electromagnetic waves that propagatelongitudinally on the MV power line.

In an embodiment where cable 1850, 1850A′ and 1850B′ each comprisemultiple instances of transmission mediums 1800, a poly-rod structure ofantennas 1855 can be formed such as shown in FIG. 18C. Each antenna 1855can be coupled, for example, to a horn antenna assembly as shown in FIG.20A or a pie-pan antenna assembly (not shown) for radiating multiplewireless signals. Alternatively, the antennas 1855 can be used as stubantennas in FIG. 20B. The microwave apparatus of FIGS. 20A-20B can beconfigured to adjust the guided electromagnetic waves to beam steer thewireless signals emitted by the antennas 1855. One or more of theantennas 1855 can also be used for inducing guided electromagnetic waveson a power line.

Turning now to FIG. 20C, a block diagram of an example, non-limitingembodiment of a communication network 2000 in accordance with variousaspects described herein is shown. In one embodiment, for example, thewaveguide system 1602 of FIG. 16A can be incorporated into networkinterface devices (NIDs) such as NIDs 2010 and 2020 of FIG. 20C. A NIDhaving the functionality of waveguide system 1602 can be used to enhancetransmission capabilities between customer premises 2002 (enterprise orresidential) and a pedestal 2004 (sometimes referred to as a servicearea interface or SAI).

In one embodiment, a central office 2030 can supply one or more fibercables 2026 to the pedestal 2004. The fiber cables 2026 can providehigh-speed full-duplex data services (e.g., 1-100 Gbps or higher) tomini-DSLAMs 2024 located in the pedestal 2004. The data services can beused for transport of voice, internet traffic, media content services(e.g., streaming video services, broadcast TV), and so on. In prior artsystems, mini-DSLAMs 2024 typically connect to twisted pair phone lines(e.g., twisted pairs included in category 5e or Cat. 5e unshieldedtwisted-pair (UTP) cables that include an unshielded bundle of twistedpair cables, such as 24 gauge insulated solid wires, surrounded by anouter insulating sheath), which in turn connect to the customer premises2002 directly. In such systems, DSL data rates taper off at 100 Mbps orless due in part to the length of legacy twisted pair cables to thecustomer premises 2002 among other factors.

The embodiments of FIG. 20C, however, are distinct from prior art DSLsystems. In the illustration of FIG. 20C, a mini-DSLAM 2024, forexample, can be configured to connect to NID 2020 via cable 1850 (whichcan represent in whole or in part any of the cable embodiments describedin relation to FIGS. 18A and 18B singly or in combination). Utilizingcable 1850 between customer premises 2002 and a pedestal 2004, enablesNIDs 2010 and 2020 to transmit and receive guide electromagnetic wavesfor uplink and downlink communications. Based on embodiments previouslydescribed, cable 1850 can be exposed to rain, or can be buried withoutadversely affecting electromagnetic wave propagation either in adownlink path or an uplink path so long as the electric field profile ofsuch waves in either direction is confined at least in part or entirelywithin inner layers of cable 1850. In the present illustration, downlinkcommunications represents a communication path from the pedestal 2004 tocustomer premises 2002, while uplink communications represents acommunication path from customer premises 2002 to the pedestal 2004. Inan embodiment where cable 1850 includes an inner conductor, cable 1850can also serve the purpose of supplying power to the NID 2010 and 2020and other equipment of the customer premises 2002 and the pedestal 2004.

In customer premises 2002, DSL signals can originate from a DSL modem2006 (which may have a built-in router and which may provide wirelessservices such as WiFi to user equipment shown in the customer premises2002). The DSL signals can be supplied to NID 2010 by a twisted pairphone 2008. The NID 2010 can utilize the integrated waveguide 1602 tolaunch within cable 1850 guided electromagnetic waves 2014 directed tothe pedestal 2004 on an uplink path. In the downlink path, DSL signalsgenerated by the mini-DSLAM 2024 can flow through a twisted pair phoneline 2022 to NID 2020. The waveguide system 1602 integrated in the NID2020 can convert the DSL signals, or a portion thereof, from electricalsignals to guided electromagnetic waves 2014 that propagate within cable1850 on the downlink path. To provide full duplex communications, theguided electromagnetic waves 2014 on the uplink can be configured tooperate at a different carrier frequency and/or a different modulationapproach than the guided electromagnetic waves 2014 on the downlink toreduce or avoid interference. Additionally, on the uplink and downlinkpaths, the guided electromagnetic waves 2014 are guided by a coresection of cable 1850, as previously described, and such waves can beconfigured to have a field intensity profile that confines the guideelectromagnetic waves in whole or in part in the inner layers of cable1850. Although the guided electromagnetic waves 2014 are shown outsideof cable 1850, the depiction of these waves is for illustration purposesonly. For this reason, the guided electromagnetic waves 2014 are drawnwith “hash marks” to indicate that they are guided by the inner layersof cable 1850.

On the downlink path, the integrated waveguide system 1602 of NID 2010receives the guided electromagnetic waves 2014 generated by NID 2020 andconverts them back to DSL signals conforming to the requirements of theDSL modem 2006. The DSL signals are then supplied to the DSL modem 2006via a set of twisted pair wires of phone line 2008 for processing.Similarly, on the uplink path, the integrated waveguide system 1602 ofNID 2020 receives the guided electromagnetic waves 2014 generated by NID2010 and converts them back to DSL signals conforming to therequirements of the mini-DSLAM 2024. The DSL signals are then suppliedto the mini-DSLAM 2024 via a set of twisted pair wires of phone line2022 for processing. Because of the short length of phone lines 2008 and2022, the DSL modem 2006 and the mini-DSLAM 2024 can send and receiveDSL signals between themselves on the uplink and downlink at very highspeeds (e.g., 1 Gbps to 60 Gbps or more). Consequently, the uplink anddownlink paths can in most circumstances exceed the data rate limits oftraditional DSL communications over twisted pair phone lines.

Typically, DSL devices are configured for asymmetric data rates becausethe downlink path usually supports a higher data rate than the uplinkpath. However, cable 1850 can provide much higher speeds both on thedownlink and uplink paths. With a firmware update, a legacy DSL modem2006 such as shown in FIG. 20C can be configured with higher speeds onboth the uplink and downlink paths. Similar firmware updates can be madeto the mini-DSLAM 2024 to take advantage of the higher speeds on theuplink and downlink paths. Since the interfaces to the DSL modem 2006and mini-DSLAM 2024 remain as traditional twisted pair phone lines, nohardware change is necessary for a legacy DSL modem or legacy mini-DSLAM other than firmware changes and the addition of the NIDs 2010 and2020 to perform the conversion from DSL signals to guidedelectromagnetic waves 2014 and vice-versa. The use of NIDs enables areuse of legacy modems 2006 and mini-DSLAMs 2024, which in turn cansubstantially reduce installation costs and system upgrades. For newconstruction, updated versions of mini-DSLAMs and DSL modems can beconfigured with integrated waveguide systems to perform the functionsdescribed above, thereby eliminating the need for NIDs 2010 and 2020with integrated waveguide systems. In this embodiment, an updatedversion of modem 2006 and updated version of mini-DSLAM 2024 wouldconnect directly to cable 1850 and communicate via bidirectional guidedelectromagnetic wave transmissions, thereby averting a need fortransmission or reception of DSL signals using twisted pair phone lines2008 and 2022.

In an embodiment where use of cable 1850 between the pedestal 2004 andcustomer premises 2002 is logistically impractical or costly, NID 2010can be configured instead to couple to a cable 1850′ (similar to cable1850 of the subject disclosure) that originates from a waveguide 108 ona utility pole 118, and which may be buried in soil before it reachesNID 2010 of the customer premises 2002. Cable 1850′ can be used toreceive and transmit guided electromagnetic waves 2014′ between the NID2010 and the waveguide 108. Waveguide 108 can connect via waveguide 106,which can be coupled to base station 104. Base station 104 can providedata communication services to customer premises 2002 by way of itsconnection to central office 2030 over fiber 2026′. Similarly, insituations where access from the central office 2030 to pedestal 2004 isnot practical over a fiber link, but connectivity to base station 104 ispossible via fiber link 2026′, an alternate path can be used to connectto NID 2020 of the pedestal 2004 via cable 1850″ (similar to cable 1850of the subject disclosure) originating from pole 116. Cable 1850″ canalso be buried before it reaches NID 2020.

Turning now to FIGS. 20D and 20E, diagrams of example, non-limitingembodiments of antenna mounts that can be used in the communicationnetwork 2000 of FIG. 20C (or other suitable communication networks) inaccordance with various aspects described herein are shown. In someembodiments, an antenna mount 2053 can be coupled to a medium voltagepower line by way of an inductive power supply that supplies energy toone or more waveguide systems (not shown) integrated in the antennamount 2053 as depicted in FIG. 20D. The antenna mount 2053 can includean array of dielectric antennas 1901 (e.g., 16 antennas) such as shownby the top and side views depicted in FIG. 20F. The dielectric antennas1901 shown in FIG. 20F can be small in dimension as illustrated by apicture comparison between groups of dielectric antennas 1901 and aconventional ballpoint pen. In other embodiments, a pole mounted antenna2054 can be used as depicted in FIG. 20D. In yet other embodiments, anantenna mount can be attached to a pole with an arm assembly. In otherembodiments, an antenna mount can be placed on a top portion of a polecoupled to a cable 1800 or 1836 such as the cables as described in thesubject disclosure.

The array of dielectric antennas 1901 of the antenna mount of FIG. 20Dcan include one or more waveguide systems as described in the subjectdisclosure by way of FIGS. 1-20. The waveguide systems can be configuredto perform beam steering with the array of dielectric antennas 1901 (fortransmission or reception of wireless signals). Alternatively, eachdielectric antenna 1901 can be utilized as a separate sector forreceiving and transmitting wireless signals. In other embodiments, theone or more waveguide systems integrated in the antenna mount of FIG.20D can be configured to utilize combinations of the dielectric antennas1901 in a wide range of multi-input multi-output (MIMO) transmission andreception techniques. The one or more waveguide systems integrated inthe antenna mount of FIG. 20D can also be configured to applycommunication techniques such as SISO, SIMO, MISO, MIMO, signaldiversity (e.g., frequency, time, space, polarization, or other forms ofsignal diversity techniques), and so on, with any combination of thedielectric antennas 1901 in any of the antenna mount of FIG. 20D. In yetother embodiments, the antenna mount of FIG. 20D can be adapted with twoor more stacks of the antenna arrays shown in FIG. 20E.

FIGS. 21A and 21B describe embodiments for downlink and uplinkcommunications. Method 2100 of FIG. 21A can begin with step 2102 whereelectrical signals (e.g., DSL signals) are generated by a DSLAM (e.g.,mini-DSLAM 2024 of pedestal 2004 or from central office 2030), which areconverted to guided electromagnetic waves 2014 at step 2104 by NID 2020and which propagate on a transmission medium such as cable 1850 forproviding downlink services to the customer premises 2002. At step 2108,the NID 2010 of the customer premises 2002 converts the guidedelectromagnetic waves 2014 back to electrical signals (e.g., DSLsignals) which are supplied at step 2110 to customer premises equipment(CPE) such as DSL modem 2006 over phone line 2008. Alternatively, or incombination, power and/or guided electromagnetic waves 2014′ can besupplied from a power line 1850′ of a utility grid (having an innerwaveguide as illustrated in FIG. 18G or 18H) to NID 2010 as an alternateor additional downlink (and/or uplink) path.

At step 2122 of method 2120 of FIG. 21B, the DSL modem 2006 can supplyelectrical signals (e.g., DSL signals) via phone line 2008 to NID 2010,which in turn at step 2124, converts the DSL signals to guidedelectromagnetic waves directed to NID 2020 by way of cable 1850. At step2128, the NID 2020 of the pedestal 2004 (or central office 2030)converts the guided electromagnetic waves 2014 back to electricalsignals (e.g., DSL signals) which are supplied at step 2129 to a DSLAM(e.g., mini-DSLAM 2024). Alternatively, or in combination, power andguided electromagnetic waves 2014′ can be supplied from a power line1850′ of a utility grid (having an inner waveguide as illustrated inFIG. 18G or 18H) to NID 2020 as an alternate or additional uplink(and/or downlink) path.

Turning now to FIG. 21C, a block diagram 2151 illustrating an example,non-limiting embodiment of electric field characteristics of a hybridwave versus a Goubau wave in accordance with various aspects describedherein is shown. Diagram 2158 shows a distribution of energy betweenHE11 mode waves and Goubau waves for an insulated conductor. The energyplots of diagram 2158 assume that the amount of power used to generatethe Goubau waves is the same as the HE11 waves (i.e., the area under theenergy curves is the same). In the illustration of diagram 2158, Goubauwaves have a steep drop in power when Goubau waves extend beyond theouter surface of an insulated conductor, while HE11 waves have asubstantially lower drop in power beyond the insulation layer.Consequently, Goubau waves have a higher concentration of energy nearthe insulation layer than HE11 waves. Diagram 2167 depicts similarGoubau and HE11 energy curves when a water film is present on the outersurface of the insulator. The difference between the energy curves ofdiagrams 2158 and 2167 is that the drop in power for the Goubau and theHE11 energy curves begins on an outer edge of the insulator for diagram2158 and on an outer edge of the water film for diagram 2167. The energycurves diagrams 2158 and 2167, however, depict the same behavior. Thatis, the electric fields of Goubau waves are tightly bound to theinsulation layer, which when exposed to water results in greaterpropagation losses than electric fields of HE11 waves having a higherconcentration outside the insulation layer and the water film. Theseproperties are depicted in the HE11 and Goubau diagrams 2168 and 2159,respectively.

By adjusting an operating frequency of HE11 waves, e-fields of HE11waves can be configured to extend substantially above a thin water filmas shown in block diagram 2169 of FIG. 21D having a greater accumulatedfield strength in areas in the air when compared to fields in theinsulator and a water layer surrounding the outside of the insulator.FIG. 21D depicts a wire having a radius of 1 cm and an insulation radiusof 1.5 cm with a dielectric constant of 2.25. As the operating frequencyof HE11 waves is reduced, the e-fields extend outwardly expanding thesize of the wave mode. At certain operating frequencies (e.g., 3 GHz)the wave mode expansion can be substantially greater than the diameterof the insulated wire and any obstructions that may be present on theinsulated wire.

By having e-fields that are perpendicular to a water film and by placingmost of its energy outside the water film, HE11 waves have lesspropagation loss than Goubau waves when a transmission medium issubjected to water or other obstructions. Although Goubau waves haveradial e-fields which are desirable, the waves are tightly coupled tothe insulation layer, which results in the e-fields being highlyconcentrated in the region of an obstruction. Consequently, Goubau wavesare still subject to high propagation losses when an obstruction such asa water film is present on the outer surface of an insulated conductor.

Turning now to FIGS. 22A and 22B, block diagrams illustrating example,non-limiting embodiments of a waveguide system 2200 for launching hybridwaves in accordance with various aspects described herein is shown. Thewaveguide system 2200 can comprise probes 2202 coupled to a slideable orrotatable mechanism 2204 that enables the probes 2202 to be placed atdifferent positions or orientations relative to an outer surface of aninsulated conductor 2208. The mechanism 2204 can comprise a coaxial feed2206 or other coupling that enables transmission of electromagneticwaves by the probes 2202. The coaxial feed 2206 can be placed at aposition on the mechanism 2204 so that the path difference between theprobes 2202 is one-half a wavelength or some odd integer multiplethereof. When the probes 2202 generate electromagnetic signals ofopposite phase, electromagnetic waves can be induced on the outersurface of the insulated conductor 2208 having a hybrid mode (such as anHE11 mode).

The mechanism 2204 can also be coupled to a motor or other actuator (notshown) for moving the probes 2202 to a desirable position. In oneembodiment, for example, the waveguide system 2200 can comprise acontroller that directs the motor to rotate the probes 2202 (assumingthey are rotatable) to a different position (e.g., east and west) togenerate electromagnetic waves that have a horizontally polarized HE11mode. To guide the electromagnetic waves onto the outer surface of theinsulated conductor 2208, the waveguide system 2200 can further comprisea tapered horn 2210 shown in FIG. 22B. The tapered horn 2210 can becoaxially aligned with the insulated conductor 2208. To reduce thecross-sectional dimension of the tapered horn 2210, an additionalinsulation layer (not shown) can placed on the insulated conductor 2208.The additional insulation layer can be similar to the tapered insulationlayer 1879 shown in FIGS. 18G and 18H. The additional insulation layercan have a tapered end that points away from the tapered horn 2210. Thetapered insulation layer 1879 can reduce a size of an initialelectromagnetic wave launched according to an HE11 mode. As theelectromagnetic waves propagate towards the tapered end of theinsulation layer, the HE11 mode expands until it reaches its full size.In other embodiments, the waveguide system 2200 may not need to use thetapered insulation layer 1879.

HE11 mode waves can be used to mitigate obstructions such as rain water.For example, suppose that rain water has caused a water film to surroundan outer surface of the insulated conductor 2208. Further assume thatwater droplets have collected at the bottom of the insulated conductor2208. The water film occupies a small fraction of the total HE11 wave.Also, by having horizontally polarized HE11 waves, the water dropletsare in a least-intense area of the HE11 waves reducing losses caused bythe droplets. Consequently, the HE11 waves experience much lowerpropagation losses than Goubau waves or waves having a mode that istightly coupled to the insulated conductor 2208 and thus greater energyin the areas occupied by the water.

It is submitted that the waveguide system 2200 of FIGS. 22A-22B can bereplaced with other waveguide systems of the subject disclosure capableof generating electromagnetic waves having an HE mode. For example, thewaveguide system 1865′ of FIG. 18K can be configured to generateelectromagnetic waves having an HE mode. In an embodiment, two or moreMMICs 1870 of the waveguide system 1865′ can be configured to generateelectromagnetic waves of opposite phase to generate polarized e-fieldssuch as those present in an HE mode. In another embodiment, differentpairs of MMICs 1870 can be selected to generate HE waves that arepolarized at different spatial positions (e.g., north and south, westand east, northwest and southeast, northeast and southeast, or othersub-fractional coordinates). Additionally, the waveguide systems ofFIGS. 18D-18K can be configured to launch electromagnetic waves havingan HE mode onto the core 1852 of one or more embodiments of cable 1850suitable for propagating HE mode waves.

Although HE waves can have desirable characteristics for mitigatingobstructions on a transmission medium, it is submitted that certain wavemodes having a cutoff frequency (e.g., TE modes, TM modes orcombinations thereof) may also exhibit waves that are sufficiently largeand have polarized e-fields that are orthogonal (or approximatelyorthogonal) to a region of an obstruction enabling their use formitigating propagation losses caused by the obstruction.

Turning to the illustration of FIG. 23A, the waveguide 2522 covers afirst region 2506 of a core 2528. Within the first region 2506,waveguide 2522 has an outer surface 2522A and an inner surface 2523. Theinner surface 2523 of the waveguide 2522 can be constructed from ametallic material or other material that reflects electromagnetic wavesand thereby enables the waveguide 2522 to be configured at step 2404 toguide the first electromagnetic wave 2502 towards the core 2528. Thecore 2528 can comprise a dielectric core (as described in the subjectdisclosure) that extends to the inner surface 2523 of the waveguide2522. In other embodiments, the dielectric core can be surrounded bycladding (such as shown in FIG. 18A), whereby the cladding extends tothe inner surface 2523 of the waveguide 2522. In yet other embodiments,the core 2528 can comprise an insulated conductor, where the insulationextends to the inner surface 2523 of the waveguide 2522. In thisembodiment, the insulated conductor can be a power line, a coaxialcable, or other types of insulated conductors.

In the first region 2506, the core 2528 comprises an interface 2526 forreceiving the first electromagnetic wave 2502. In one embodiment, theinterface 2526 of the core 2528 can be configured to reduce reflectionsof the first electromagnetic wave 2502. In one embodiment, the interface2526 can be a tapered structure to reduce reflections of the firstelectromagnetic wave 2502 from a surface of the core 2528. Otherstructures can be used for the interface 2526. For example, theinterface 2526 can be partially tapered with a rounded point.Accordingly, any structure, configuration, or adaptation of theinterface 2526 that can reduced reflections of the first electromagneticwave 2502 is contemplated by the subject disclosure. The firstelectromagnetic wave 2502 induces (or otherwise generates) a secondelectromagnetic wave 2504 that propagates within the core 2528 in thefirst region 2506 covered by the waveguide 2522. The inner surface 2523of the waveguide 2522 confines the second electromagnetic wave 2504within the core 2528.

A second region 2508 of the core 2528 is not covered by the waveguide2522, and is thereby exposed to the environment (e.g., air). In thesecond region 2508, the second electromagnetic wave 2504 expandsoutwardly beginning from the discontinuity between the edge of thewaveguide 2522 and the exposed core 2528. To reduce the radiation intothe environment from the second electromagnetic wave 2504, the core 2528can be configured to have a tapered structure 2520. As the secondelectromagnetic wave 2504 propagates along the tapered structure 2520,the second electromagnetic wave 2504 remains substantially bound to thetapered structure 2520 thereby reducing radiation losses. The taperedstructure 2520 ends at a transition from the second region 2508 to athird region 2510. In the third region, the core has a cylindricalstructure 2529 having a diameter equal to the endpoint of the taperedstructure 2520 at the juncture between the second region 2508 and thethird region 2510. In the third region 2510 of the core 2528, the secondelectromagnetic wave 2504 experiences a low propagation loss. In oneembodiment, this can be accomplished by selecting a diameter of the core2528 that enables the second electromagnetic wave 2504 to be looselybound to the outer surface of the core 2528 in the third region 2510.Alternatively, or in combination, propagation losses of the secondelectromagnetic wave 2504 can be reduced by configuring the MMICs 2524to adjust a wave mode, wave length, operating frequency, or otheroperational parameter of the first electromagnetic wave 2502.

FIG. 24 illustrates a portion of the waveguide 2522 of FIG. 23A depictedas a cylindrical ring (that does not show the MMICs 2524 or the taperedstructure 2526 of FIG. 23A). In the simulations, a first electromagneticwave is injected at the endpoint of the core 2528 shown in FIG. 24. Thesimulation assumes no reflections of the first electromagnetic wavebased on an assumption that a tapered structure 2526 (or other suitablestructure) is used to reduce such reflections. The simulations are shownas two longitudinal cross-sectional views of the core 2528 covered inpart by waveguide section 2523A, and an orthogonal cross-sectional viewof the core 2528. In the case of the longitudinal cross-sectional views,one of the illustrations is a blown up view of a portion of the firstillustration.

As can be seen from the simulations, electromagnetic wave fields 2532 ofthe second electromagnetic wave 2504 are confined within the core 2528by the inner surface 2523 of the waveguide section 2523A. As the secondelectromagnetic wave 2504 enters the second region 2508 (no longercovered by the waveguide section 2523A), the tapered structure 2520reduces radiation losses of the electromagnetic wave fields 2532 as itexpands over the outer tapered surface of the core 2528. As the secondelectromagnetic wave 2504 enters the third region 2510, theelectromagnetic wave fields 2532 stabilize and thereafter remain looselycoupled to the core 2528 (depicted in the longitudinal and orthogonalcross-sectional views), which reduces propagation losses.

FIG. 23B provides an alternative embodiment to the tapered structure2520 in the second region 2508. The tapered structure 2520 can beavoided by extending the waveguide 2522 into the second region 2508 witha tapered structure 2522B and maintaining the diameter of the core 2528throughout the first, second and third regions 2506, 2508 and 2510 ofthe core 2528 as depicted in FIG. 23B. The horn structure 2522B can beused to reduce radiation losses of the second electromagnetic wave 2504as the second electromagnetic wave 2504 transitions from the firstregion 2506 to the second region 2508. In the third region 2510, thecore 2528 is exposed to the environment. As noted earlier, the core 2528is configured in the third region 2510 to reduce propagation losses bythe second electromagnetic wave 2504. In one embodiment, this can beaccomplished by selecting a diameter of the core 2528 that enables thesecond electromagnetic wave 2504 to be loosely bound to the outersurface of the core 2528 in the third region 2510. Alternatively, or incombination, propagation losses of the second electromagnetic wave 2504can be reduced by adjusting a wave mode, wave length, operatingfrequency, or other performance parameter of the first electromagneticwave 2502.

The waveguides 2522 of FIGS. 23A and 23B can also be adapted forreceiving electromagnetic waves. For example, the waveguide 2522 of FIG.23A can be adapted to receive an electromagnetic wave at step 2412. Thiscan be represented by an electromagnetic wave 2504 propagating in thethird region 2510 from east to west (orientation shown at bottom rightof FIGS. 23A-23B) towards the second region 2508. Upon reaching thesecond region 2508, the electromagnetic wave 2504 gradually becomes moretightly coupled to the tapered structure 2520. When it reaches theboundary between the second region 2508 and the first region 2506 (i.e.,the edge of the waveguide 2522), the electromagnetic wave 2504propagates within the core 2528 confined by the inner surface 2523 ofthe waveguide 2522. Eventually the electromagnetic wave 2504 reaches anendpoint of the tapered interface 2526 of the core 2528 and radiates asa new electromagnetic wave 2502 which is guided by the inner surface2523 of the waveguide 2522.

One or more antennas of the MMICs 2524 can be configured to receive theelectromagnetic wave 2502 thereby converting the electromagnetic wave2502 to an electrical signal at step 2414 which can be processed by aprocessing device (e.g., a receiver circuit and microprocessor). Toprevent interference between electromagnetic waves transmitted by theMMICs 2524, a remote waveguide system that transmitted theelectromagnetic wave 2504 that is received by the waveguide 2522 of FIG.23A can be adapted to transmit the electromagnetic wave 2504 at adifferent operating frequency, different wave mode, different phase, orother adjustable operational parameter to avoid interference.Electromagnetic waves can be received by the waveguide 2522 of FIG. 23Bin a similar manner as described above.

Turning now to FIG. 23C, the waveguide 2522 of FIG. 23B can be adaptedto support transmission mediums 2528 that have no endpoints such asshown in FIG. 23C. In this illustration, the waveguide 2522 comprises achamber 2525 in a first region 2506 of the core 2528. The chamber 2525creates a gap 2527 between an outer surface 2521 of the core 2528 andthe inner surface 2523 of the waveguide 2522. The gap 2527 providessufficient room for placement of the MMICs 2524 on the inner surface2523 of the waveguide 2522. To enable the waveguide 2522 to receiveelectromagnetic waves from either direction, the waveguide 2522 can beconfigured with symmetrical regions: 2508 and 2508′, 2510 and 2510′, and2512, and 2512′. In the first region 2506, the chamber 2525 of thewaveguide 2522 has two tapered structures 2522B′ and 2522B″. Thesetapered structures 2522B′ and 2522B″ enable an electromagnetic wave togradually enter or exit the chamber 2525 from either direction of thecore 2528. The MMICs 2524 can be configured with directional antennas tolaunch a first electromagnetic wave 2502 directed from east-to-west orfrom west-to-east in relation to the longitudinal view of the core 2528.Similarly, the directional antennas of the MMICs 2524 can be configuredto receive an electromagnetic waves propagating longitudinally on thecore 2528 from east-to-west or from west-to-east. The process fortransmitting electromagnetic waves is similar to that described for FIG.23B depending on whether the directional antennas of the MMICs 2524 aretransmitting from east-to-west or from west-to-east.

Although not shown, the waveguide 2522 of FIG. 23C can be configuredwith a mechanism such as one or more hinges that enable splitting thewaveguide 2522 into two parts that can be separated. The mechanism canbe used to enable installation of the waveguide 2522 onto a core 2528without endpoints. Other mechanisms for installation of the waveguide2522 of FIG. 23C on a core 2528 are contemplated by the subjectdisclosure. For example, the waveguide 2522 can be configured with aslot opening that spans the entire waveguide structure longitudinally.In a slotted design of the waveguide 2522, the regions 2522C′ and 2522Cof the waveguide 2522 can be configured so that the inner surface 2523of the waveguide 2522 is tightly coupled to the outer surface of thecore 2528. The tight coupling between the inner surface 2523 of thewaveguide 2522 the outer surface of the core 2528 prevents sliding ormovement of the waveguide 2522 relative to the core 2528. A tightcoupling in the regions 2522C′ and 2522C can also be applied to a hingeddesign of the waveguide 2522.

The waveguides 2522 shown in FIGS. 23A, 23B and 25C can be adapted toperform one or more embodiments described in other figures of thesubject disclosure. Accordingly, it is contemplated that suchembodiments can be applied to the waveguide 2522 of FIGS. 23A, 23B and23C. Additionally, any adaptations in the subject disclosure of a corecan be applied to the waveguide 2522 of FIGS. 23A, 23B and 23C.

It is further noted that the waveguide launchers 2522 of FIGS. 23A-23Cand/or other waveguide launchers described and shown in the figures ofthe subject disclosure (e.g., FIGS. 7-14, 18D-18K, 22A-22B, 23A-23C, 24and other drawings) and any methods thereof can be adapted to generatealong a transmission medium having an outer surface composed of, forexample, a dielectric material (e.g., insulation, oxidation, or othermaterial with dielectric properties) a single wave mode or combinationof wave modes that reduce propagation losses when propagating through asubstance, such as a liquid (e.g., water produced by humidity, snow,dew, sleet and/or rain), disposed on the outer surface of thetransmission medium.

Referring now to FIG. 25A, there is illustrated a diagram of an example,non-limiting embodiment of a waveguide device 2522 in accordance withvarious aspects described herein. In the illustration of FIG. 25A, thewaveguide device 2522 is coupled to a transmission medium 2542comprising a conductor 2543 and insulation layer 2543, which togetherform an insulated conductor. Although not shown, the waveguide device2522 can be constructed in two halves, which can be connected togetherat one longitudinal end with one or more mechanical hinges to enableopening a longitudinal edge at an opposite end of the one or more hingesfor placement of the waveguide device 2522 over the transmission medium2542. Once placed, one or more latches at the longitudinal edge oppositethe one or more hinges can be used to secure the waveguide device 2522to the transmission medium 2542. Other embodiments for coupling thewaveguide device 2522 to the transmission medium 2542 can be used andare therefore contemplated by the subject disclosure.

The chamber 2525 of the waveguide device 2522 of FIG. 25A includes adielectric material 2544′. The dielectric material 2544′ in the chamber2525 can have a dielectric constant similar to the dielectric constantof the dielectric layer 2544 of the insulated conductor. Additionally, adisk 2525′ having a center-hole 2525″ can be used to divide the chamber2525 in two halves for transmission or reception of electromagneticwaves. The disk 2525′ can be constructed of a material (e.g., carbon,metal or other reflective material) that does not allow electromagneticwaves to progress between the halves of the chamber 2525. The MMICs2524′ can be located inside the dielectric material 2544′ of the chamber2525 as shown in FIG. 25A. Additionally, the MMICs 2524′ can be locatednear an outer surface of the dielectric layer 2543 of the transmissionmedium 2542. FIG. 25A shows an expanded view 2524A′ of an MMIC 2524′that includes an antenna 2524B′ (such as a monopole antenna, dipoleantenna or other antenna) that can be configured to be longitudinallyaligned with the outer surface of the dielectric layer 2543 of thetransmission medium 2542. The antenna 2524B′ can be configured toradiate signals that have a longitudinal electric field directed east orwest as will be discussed shortly. It will be appreciated that otherantenna structures that can radiate signals that have a longitudinalelectric field can be used in place of the dipole antenna 2524B′ of FIG.25A.

It will be appreciated that although two MMICs 2524′ are shown in eachhalf of the chambers 2525 of the waveguide device 2522, more MMICs canbe used. For example, FIG. 18K shows a transverse cross-sectional viewof a cable (such as the transmission medium 2542) surrounded by awaveguide device with 8 MMICs located in positions: north, south, east,west, northeast, northwest, southeast, and southwest. The two MMICs2524′ shown in FIG. 25A can be viewed, for illustration purposes, asMMICs 2524′ located in the north and south positions shown in FIG. 18K.The waveguide device 2522 of FIG. 25A can be further configured withMMICs 2524′ at western and eastern positions as shown in FIG. 18K.Additionally, the waveguide device 2522 of FIG. 25A can be furtherconfigured with MMICs at northwestern, northeastern, southwestern andsoutheastern positions as shown in FIG. 18K. Accordingly, the waveguidedevice 2522 can be configured with more than the 2 MMICs shown in FIG.25A.

With this in mind, attention is now directed to FIGS. 25B, 25C, 25D,which illustrate diagrams of example, non-limiting embodiments of wavemodes and electric field plots in accordance with various aspectsdescribed herein. FIG. 25B illustrates the electric fields of a TM01wave mode. The electric fields are illustrated in a transversecross-sectional view (top) and a longitudinal cross-sectional view(below) of a coaxial cable having a center conductor with an externalconductive shield separated by insulation. FIG. 25C illustrates theelectric fields of a TM11 wave mode. The electric fields are alsoillustrated in a transverse cross-sectional view and a longitudinalcross-sectional view of a coaxial cable having a center conductor withan external conductive shield separated by an insulation. FIG. 25Dfurther illustrates the electric fields of a TM21 wave mode. Theelectric fields are illustrated in a transverse cross-sectional view anda longitudinal cross-sectional view of a coaxial cable having a centerconductor with an external conductive shield separated by an insulation.

As shown in the transverse cross-sectional view, the TM01 wave mode hascircularly symmetric electric fields (i.e., electric fields that havethe same orientation and intensity at different azimuthal angles), whilethe transverse cross-sectional views of the TM11 and TM21 wave modesshown in FIGS. 25C-25D, respectively, have non-circularly symmetricelectric fields (i.e., electric fields that have different orientationsand intensities at different azimuthal angles). Although the transversecross-sectional views of the TM11 and TM21 wave modes havenon-circularly symmetric electric fields, the electric fields in thelongitudinal cross-sectional views of the TM01, TM11 and TM21 wave modesare substantially similar with the exception that that the electricfield structure of the TM11 wave mode has longitudinal electric fieldsabove the conductor and below the conductor that point in oppositelongitudinal directions, while the longitudinal electric fields abovethe conductor and below the conductor for the TM01 and TM21 wave modespoint in the same longitudinal direction.

The longitudinal cross-sectional views of the coaxial cable of FIGS.25B, 25C and 25D can be said to have a similar structural arrangement tothe longitudinal cross-section of the waveguide device 2522 in region2506′ shown in FIG. 25A. Specifically, in FIGS. 25B, 25C and 25D thecoaxial cable has a center conductor and a shield separated byinsulation, while region 2506′ of the waveguide device 2522 has a centerconductor 2543, a dielectric layer 2544, covered by the dielectricmaterial 2544′ of the chamber 2525, and shielded by the reflective innersurface 2523 of the waveguide device 2522. The coaxial configuration inregion 2506′ of the waveguide device 2522 continues in the taperedregion 2506″ of the waveguide device 2522. Similarly, the coaxialconfiguration continues in regions 2508 and 2510 of the waveguide device2522 with the exception that no dielectric material 2544′ is present inthese regions other than the dielectric layer 2544 of the transmissionmedium 2542. At the outer region 2512, the transmission medium 2542 isexposed to the environment (e.g., air) and thus the coaxialconfiguration is no longer present.

As noted earlier, the electric field structure of a TM01 wave mode iscircularly symmetric in a transverse cross-sectional view of the coaxialcable shown in FIG. 25B. For illustration purposes, it will be assumedthat the waveguide device 2522 of FIG. 25A has 4 MMICs located innorthern, southern, western and eastern locations as depicted in FIG.18K. In this configuration, and with an understanding of thelongitudinal and transverse electric field structures of the TM01 wavemode shown in FIG. 25B, the 4 MMICs 2524′ of the waveguide device 2522in FIG. 25A can be configured to launch from a common signal source aTM01 wave mode on the transmission medium 2542. This can be accomplishedby configuring the north, south, east and west MMICs 2524′ to launchwireless signals with the same phase (polarity). The wireless signalsgenerated by the 4 MMICs 2524′ combine via superposition of theirrespective electric fields in the dielectric material 2544′ of thechamber 2525 and the dielectric layer 2544 (since both dielectricmaterials have similar dielectric constants) to form a TM01electromagnetic wave 2502′ bound to these dielectric materials with theelectric field structure shown in longitudinal and transverse views ofFIG. 25B.

The electromagnetic wave 2502′ having the TM01 wave mode in turnpropagates toward the tapered structure 2522B of the waveguide device2522 and thereby becomes an electromagnetic wave 2504′ embedded withinthe dielectric layer 2544 of the transmission medium 2542′ in region2508. In the tapered horn section 2522D the electromagnetic wave 2504′having the TM01 wave mode expands in region 2510 and eventually exitsthe waveguide device 2522 without change to the TM01 wave mode.

In another embodiment, the waveguide device 2522 can be configured tolaunch a TM11 wave mode having a vertical polarity in region 2506′. Thiscan be accomplished by configuring the MMIC 2524′ in the northernposition to radiate from a signal source a first wireless signal havinga phase (polarity) opposite to the phase (polarity) of a second wirelesssignal radiated from the same signal source by the southern MMIC 2524′.These wireless signals combine via superposition of their respectiveelectric fields to form an electromagnetic wave having a TM11 wave mode(vertically polarized) bound to the dielectric materials 2544′ and 2544with the electric field structures shown in the longitudinal andtransverse cross-sectional views shown in FIG. 25C. Similarly, thewaveguide device 2522 can be configured to launch a TM11 wave modehaving a horizontal polarity in region 2506′. This can be accomplishedby configuring the MMIC 2524′ in the eastern position to radiate a firstwireless signal having a phase (polarity) opposite to the phase(polarity) of a second wireless signal radiated by the western MMIC2524′.

These wireless signals combine via superposition of their respectiveelectric fields to form an electromagnetic wave having a TM11 wave mode(horizontally polarized) bound to the dielectric materials 2544′ and2544 with the electric field structures shown in the longitudinal andtransverse cross-sectional views shown in FIG. 25C (but with ahorizontal polarization). Since the TM11 wave mode with horizontal andvertical polarizations are orthogonal (i.e., a dot product ofcorresponding electric field vectors between any pair of these wavemodes at each point of space and time produces a summation of zero), thewaveguide device 2522 can be configured to launch these wave modessimultaneously without interference, thereby enabling wave mode divisionmultiplexing. It is further noted that the TM01 wave mode is alsoorthogonal to the TM11 and TM21 wave modes.

While the electromagnetic wave 2502′ or 2504′ having the TM11 wave modepropagates within the confines of the inner surfaces 2523 of thewaveguide device 2522 in regions 2506′, 2506″, 2508 and 2510, the TM11wave mode remains unaltered. However, when the electromagnetic wave2504′ having the TM11 wave mode exits the waveguide device 2522 inregion 2512 the inner wall 2523 is no longer present and the TM11 wavemode becomes a hybrid wave mode, specifically, an EH11 wave mode(vertically polarized, horizontally polarized, or both if twoelectromagnetic waves are launched in region 2506′).

In yet other embodiments, the waveguide device 2522 can also beconfigured to launch a TM21 wave mode in region 2506′. This can beaccomplished by configuring the MMIC 2524′ in the northern position toradiate from a signal source a first wireless signal having a phase(polarity) that is in phase (polarity) to a second wireless signalgenerated from the same signal source by the southern MMIC 2524′. At thesame time, the MMIC 2524′ in the western position is configured toradiate from the same signal source a third wireless signal that is inphase with a fourth wireless signal radiated from the same signal sourceby the MMIC 2524′ located in the eastern position. The north and southMMICs 2524′, however, generate first and second wireless signals ofopposite polarity to the polarity of the third and fourth wirelesssignals generated by the western and eastern MMICs 2524′. The fourwireless signals of alternating polarity combine via superposition oftheir respective electric fields to form an electromagnetic wave havinga TM21 wave mode bound to the dielectric materials 2544′ and 2544 withthe electric field structures shown in the longitudinal and transversecross-sectional views shown in FIG. 25D. When the electromagnetic wave2504′ exits the waveguide device 2522 it may be transformed to a hybridwave mode such as, for example, an HE21 wave mode, an EH21 wave mode, ora hybrid wave mode with a different radial mode (e.g., HE2m or EH2m,where m>1).

FIGS. 25A-25D illustrate several embodiments for launching TM01, EH11,and other hybrid wave modes utilizing the waveguide device 2522 of FIG.25A. With an understanding of the electric field structures of otherwave modes that propagate on a coaxial cable (e.g., TM12, TM22, and soon), the MMICs 2524′ can be further configured in other ways to launchother wave modes (e.g., EH12, HE22, etc.) that have a low intensityz-field component and phi-field component in the electric fieldstructures near the outer surface of a transmission medium 2542, whichis useful for mitigating propagation losses due to a substance such aswater, droplets or other substances that can cause an attenuation of theelectric fields of an electromagnetic wave propagating along the outersurface of the transmission medium 2542.

FIG. 26 illustrates a flow diagram of an example, non-limitingembodiment of a method 2560 for sending and receiving electromagneticwaves. Method 2560 can be applied to waveguides 2522 of FIGS. 23A-23C,24 and 25A and/or other waveguide systems or launchers described andshown in the figures of the subject disclosure (e.g., FIGS. 7-14,18D-18K, 22A-22B and other drawings) for purposes of launching orreceiving substantially orthogonal wave modes such as those shown inFIG. 27. FIG. 27 depicts three cross-sectional views of an insulatedconductor where a TM00 fundamental wave mode, an HE11 wave mode withhorizontal polarization, and an HE11 wave mode with verticalpolarization, propagates respectively. The electric field structureshown in FIG. 27 can vary over time and is therefore an illustrativerepresentation at a certain instance or snapshot in time. The wave modesshown in FIG. 27 are orthogonal to each other. That is, a dot product ofcorresponding electric field vectors between any pair of the wave modesat each point of space and time produces a summation of zero. Thisproperty enables the TM00 wave mode, the HE11 wave mode with horizontalpolarization, and the HE11 wave mode with vertical polarization topropagate simultaneously along a surface of the same transmission mediumin the same frequency band without signal interference.

With this in mind, method 2560 can begin at step 2562 where a waveguidesystem of the subject disclosure can be adapted to receive communicationsignals from a source (e.g., a base station, a wireless signaltransmitted by a mobile or stationary device to an antenna of thewaveguide system as described in the subject disclosure, or by way ofanother communication source.). The communication signals can be, forexample, communication signals modulated according to a specificsignaling protocol (e.g., LTE, 5G, DOCSIS, DSL, etc.) operating in anative frequency band (e.g., 900 MHz, 1.9 GHz, 2.4 GHz, 5 GHz, etc.),baseband signals, analog signals, other signals, or any combinationsthereof. At step 2564, the waveguide system can be adapted to generateor launch on a transmission medium a plurality of electromagnetic wavesaccording to the communication signals by up-converting (or in someinstances down-converting) such communication signals to one or moreoperating frequencies of the plurality of electromagnetic waves. Thetransmission medium can be an insulated conductor as shown in FIG. 28,or an uninsulated conductor that is subject to environmental exposure tooxidation (or other chemical reaction based on environmental exposure)as shown in FIGS. 29 and 30. In other embodiments, the transmissionmedium can be a dielectric material such as a dielectric core describedin FIG. 18A.

To avoid interference, the waveguide system can be adapted tosimultaneously launch at step 2564 a first electromagnetic wave using aTM00 wave mode, a second electromagnetic wave using an HE11 wave modewith horizontal polarization, and a third electromagnetic wave using anHE11 wave mode with vertical polarization—see FIG. 27. Since the first,second and third electromagnetic waves are orthogonal (i.e.,non-interfering) they can be launched in the same frequency band withoutinterference or with a small amount of acceptable interference. Thecombined transmission of three orthogonal electromagnetic wave modes inthe same frequency band constitutes a form of wave mode divisionmultiplexing, which provides a means for increasing the informationbandwidth by a factor of three. By combining the principles of frequencydivision multiplexing with wave mode division multiplexing, bandwidthcan be further increased by configuring the waveguide system to launch afourth electromagnetic wave using a TM00 wave mode, a fifthelectromagnetic wave using an HE11 wave mode with horizontalpolarization, and a sixth electromagnetic wave using an HE11 wave modewith vertical polarization in a second frequency band that does notoverlap with the first frequency band of the first, second and thirdorthogonal electromagnetic waves. It will be appreciated that othertypes of multiplexing could be additionally or alternatively used withwave mode division multiplexing without departing from exampleembodiments.

To illustrate this point, suppose each of three orthogonalelectromagnetic waves in a first frequency band supports 1 GHz oftransmission bandwidth. And further suppose each of three orthogonalelectromagnetic waves in a second frequency band also supports 1 GHz oftransmission bandwidth. With three wave modes operating in two frequencybands, 6 GHz of information bandwidth is possible for conveyingcommunication signals by way of electromagnetic surface waves utilizingthese wave modes. With more frequency bands, the bandwidth can beincreased further.

Now suppose a transmission medium in the form of an insulated conductor(see FIG. 28) is used for surface wave transmissions. Further supposethe transmission medium has a dielectric layer with thicknessproportional to the conductor radius (e.g., a conductor having a 4 mmradius and an insulation layer with a 4 mm thickness). With this type oftransmission medium, the waveguide system can be configured to selectfrom several options for transmitting electromagnetic waves. Forexample, the waveguide system can be configured at step 2564 to transmitfirst through third electromagnetic waves using wave mode divisionmultiplexing at a first frequency band (e.g., at 1 GHz), third throughfourth electromagnetic waves using wave mode division multiplexing at asecond frequency band (e.g., at 2.1 GHz), seventh through ninthelectromagnetic waves using wave mode division multiplexing at a thirdfrequency band (e.g., at 3.2 GHz), and so on. Assuming eachelectromagnetic wave supports 1 GHz of bandwidth, collectively the firstthrough ninth electromagnetic waves can support 9 GHz of bandwidth.

Alternatively, or contemporaneous with transmitting electromagneticwaves with orthogonal wave modes at step 2564, the waveguide system canbe configured at step 2564 to transmit on the insulated conductor one ormore high frequency electromagnetic waves (e.g., millimeter waves). Inone embodiment, the one or more high frequency electromagnetic waves canbe configured in non-overlapping frequencies bands according to one ormore corresponding wave modes that are less susceptible to a water filmsuch as a TM0m wave mode and EH1m wave mode (where m>0), or an HE2m wavemode (where m>1) as previously described. In other embodiments, thewaveguide system can instead be configured to transmit one or more highfrequency electromagnetic waves in non-overlapping frequency bandsaccording to one or more corresponding wave modes that have longitudinaland/or azimuthal fields near the surface of the transmission medium thatmay be susceptible to water, but nonetheless exhibit low propagationlosses when the transmission medium is dry. A waveguide system can thusbe configured to transmit several combinations of wave modes on aninsulated conductor (as well as a dielectric-only transmission mediumsuch as a dielectric core) when the insulated conductor is dry.

Now suppose a transmission medium in the form of an uninsulatedconductor (see FIGS. 29-30) is used for surface wave transmissions.Further consider that the uninsulated conductor or bare conductor isexposed to an environment subject to various levels of moisture and/orrain (as well as air and atmospheric gases like oxygen). Uninsulatedconductors, such as overhead power lines and other uninsulated wires,are often made of aluminum which is sometimes reinforced with steel.Aluminum can react spontaneously with water and/or air to form aluminumoxide. An aluminum oxide layer can be thin (e.g., nano to micrometers inthickness). An aluminum oxide layer has dielectric properties and cantherefore serve as a dielectric layer. Accordingly, uninsulatedconductors can propagate not only TM00 wave modes, but also other wavemodes such as an HE11 wave mode with horizontal polarization, and anHE11 wave mode with vertical polarization at high frequencies based atleast in part on the thickness of the oxide layer. Accordingly,uninsulated conductors having an environmentally formed dielectric layersuch as an oxide layer can be used for transmitting electromagneticwaves using wave mode division multiplexing and frequency divisionmultiplexing. Other electromagnetic waves having a wave mode (with orwithout a cutoff frequency) that can propagate on an oxide layer arecontemplated by the subject disclosure and can be applied to theembodiments described in the subject disclosure.

In one embodiment, the term “environmentally formed dielectric layer”can represent an uninsulated conductor that is exposed to an environmentthat is not artificially created in a laboratory or other controlledsetting (e.g., bare conductor exposed to air, humidity, rain, etc. on autility pole or other exposed environment). In other embodiments, anenvironmentally formed dielectric layer can be formed in a controlledsetting such as a manufacturing facility that exposes uninsulatedconductors to a controlled environment (e.g., controlled humidity, orother gaseous substance) that forms a dielectric layer on the outersurface of the uninsulated conductor. In yet another alternativeembodiment, the uninsulated conductor can also be “doped” withparticular substances/compounds (e.g., a reactant) that facilitatechemical reactions with other substances/compounds that are eitheravailable in a natural environment or in an artificially createdlaboratory or controlled setting, thereby resulting in the creation ofthe environmentally formed dielectric layer.

Wave mode division multiplexing and frequency division multiplexing canprove useful in mitigating obstructions such as water accumulating on anouter surface of a transmission medium. To determine if mitigating anobstruction is necessary, a waveguide system can be configured at step2566 to determine if an obstruction is present on the transmissionmedium. A film of water (or water droplets) collected on an outersurface of the transmission medium due to rain, condensation, and/orexcess humidity can be one form of an obstruction that can causepropagation losses in electromagnetic waves if not mitigated. A splicingof a transmission medium or other object coupled to the outer surface ofthe transmission medium can also serve as an obstruction.

Obstructions can be detected by a source waveguide system that transmitselectromagnetic waves on a transmission medium and measures reflectedelectromagnetic waves based on these transmissions. Alternatively, or incombination, the source waveguide system can detect obstructions byreceiving communication signals (wireless or electromagnetic waves) froma recipient waveguide system that receives and performs quality metricson electromagnetic waves transmitted by the source waveguide system.When an obstruction is detected at step 2566, the waveguide system canbe configured to identify options to update, modify, or otherwise changethe electromagnetic waves being transmitted.

Suppose, for example, that in the case of an insulated conductor, thewaveguide system had launched at step 2564 a high order wave mode suchas TM01 wave mode with a frequency band that starts at 30 GHz having alarge bandwidth (e.g., 10 GHz) when the insulated conductor is dry. Forillustration purposes, a 10 GHz bandwidth will be assumed for anelectromagnetic wave having a TM01 wave mode.

Although it was noted earlier in the subject disclosure that a TM01 wavemode has a desirable electric field alignment that is not longitudinaland not azimuthal near the outer surface, it can nonetheless be subjectto some signal attenuation which in turn reduces its operating bandwidthwhen a water film (or droplets) accumulates on the insulated conductor.An electromagnetic wave having a TM01 wave mode with a bandwidth ofapproximately 10 GHz (30 to 40 GHz) on a dry insulated conductor candrop to a bandwidth of approximately 1 GHz (30 to 31 GHz) when theinsulated conductor is wet. To mitigate the loss in bandwidth, thewaveguide system can be configured to launch electromagnetic waves atmuch lower frequencies (e.g., less than 6 GHz) using wave mode divisionmultiplexing and frequency division multiplexing.

For example, the waveguide system can be configured to transmit a firstset of electromagnetic waves; specifically, a first electromagnetic wavehaving a TM00 wave mode, a second electromagnetic wave having an HE11wave mode with horizontal polarization, and a third electromagnetic wavehaving an HE11 wave mode with vertical polarization, eachelectromagnetic wave having a center frequency at 1 GHz. Assuming auseable frequency band from 500 MHz to 1.5 GHz to convey communicationsignals, each electromagnetic wave can provide 1 GHz of bandwidth, andcollectively 3 GHz of system bandwidth.

Suppose also the waveguide system is configured to transmit a second setof electromagnetic waves; specifically, a fourth electromagnetic wavehaving a TM00 wave mode, a fifth electromagnetic wave having an HE11wave mode with horizontal polarization, and a sixth electromagnetic wavehaving an HE11 wave mode with vertical polarization, eachelectromagnetic wave having a center frequency at 2.1 GHz. Assuming afrequency band from 1.6 GHz to 2.6 GHz, with a guard band of 100 MHzbetween the first and second sets of electromagnetic waves, eachelectromagnetic wave can provide 1 GHz of bandwidth, and collectively 3GHz of additional bandwidth, thereby now providing up to 6 GHz of systembandwidth.

Further suppose the waveguide system is also configured to transmit athird set of electromagnetic waves; specifically, a seventhelectromagnetic wave having a TM00 wave mode, an eighth electromagneticwave having an HE11 wave mode with horizontal polarization, and a ninthelectromagnetic wave having an HE11 wave mode with verticalpolarization, each electromagnetic wave having a center frequency at 3.2GHz. Assuming a frequency band from 2.7 GHz to 3.7 GHz, with a guardband of 100 MHz between the second and third sets of electromagneticwaves, each electromagnetic wave can provide 1 GHz of bandwidth, andcollectively 3 GHz of additional bandwidth, thereby now providing up to9 GHz of system bandwidth.

The combination of the TM01 wave mode, and the three sets ofelectromagnetic waves configured for wave mode division multiplexing andfrequency division multiplexing, provide a total system bandwidth of 10GHz, thereby restoring a bandwidth of 10 GHz previously available whenthe high frequency electromagnetic wave having the TM01 wave mode waspropagating on a dry insulated conductor. FIG. 31 illustrates a processfor performing mitigation of a TM01 wave mode subject to an obstructionsuch as a water film. FIG. 31 illustrates a transition from a dryinsulated conductor that supports a high bandwidth TM01 wave mode to awet insulated conductor that supports a lower bandwidth TM01 wave modethat is combined with low frequency TM00 and HE11 wave modes configuredaccording to wave mode division multiplexing (WMDM) and frequencydivision multiplexing (FDM) schemes to restore losses in systembandwidth.

Consider now an uninsulated conductor where the waveguide system hadlaunched at step 2564 a TM00 wave mode with a frequency band that startsat 10 GHz having a large bandwidth (e.g., 10 GHz). Suppose now thattransmission medium propagating the 10 GHz TM00 wave mode is exposed toan obstruction such as water. As noted earlier, a high frequency TM00wave mode on an insulated conductor is subject to a substantial amountof signal attenuation (e.g., 45 dB/M at 10 GHz) when a water film (ordroplets) accumulates on the outer surface of the insulated conductor.Similar attenuations will be present for a 10 GHz (or greater) TM00 wavemode propagating on an “uninsulated” conductor. An environmentallyexposed uninsulated conductor (e.g., aluminum), however, can have anoxide layer formed on the outer surface which can serve as a dielectriclayer that supports wave modes other than TM00 (e.g., HE11 wave modes).It is further noted that at lower frequencies a TM00 wave modepropagating on an insulated conductor exhibits a much lower attenuation(e.g., 0.62 dB/M at 4 GHz). A TM00 wave mode operating at less than 6GHz would similarly exhibit low propagation losses on an uninsulatedconductor. Accordingly, to mitigate the loss in bandwidth, the waveguidesystem can be configured to launch electromagnetic waves having a TM00wave mode at lower frequencies (e.g., 6 GHz or less) and electromagneticwaves having an HE11 wave mode configured for WMDM and FDM at higherfrequencies.

Referring back to FIG. 26, suppose then that the waveguide systemdetects an obstruction such as water at step 2566 on an environmentallyexposed uninsulated conductor. A waveguide system can be configured tomitigate the obstruction by transmitting a first electromagnetic waveconfigured with a TM00 wave mode having a center frequency at 2.75 GHz.Assuming a useable frequency band from 500 MHz to 5.5 GHz to conveycommunication signals, the electromagnetic waves can provide 5 GHz ofsystem bandwidth.

FIG. 32 illustrates a process for performing mitigation of a highfrequency TM00 wave mode subject to an obstruction such as a water filmdetected at step 2566. FIG. 31 illustrates a transition from a dryuninsulated conductor that supports a high bandwidth TM00 wave mode to awet uninsulated conductor that combines a low frequency TM00 wave modeand high frequency HE11 wave modes configured according to WMDM and FDMschemes to restore losses in system bandwidth.

It will be appreciated that the aforementioned mitigation techniques arenon-limiting. For example, the center frequencies described above candiffer between systems. Additionally, the original wave mode used beforean obstruction is detected can differ from the illustrations above. Forexample, in the case of an insulated conductor an EH11 wave mode can beused singly or in combination with a TM01 wave mode. It is alsoappreciated that WMDM and FDM techniques can be used to transmitelectromagnetic waves at all times and not just when an obstruction isdetected at step 2566. It is further appreciated that other wave modesthat can support WMDM and/or FDM techniques can be applied to and/orcombined with the embodiments described in the subject disclosure, andare therefore contemplated by the subject disclosure.

Referring back to FIG. 26, once a mitigation scheme using WMDM and/orFDM has been determined in accordance with the above illustrations, thewaveguide system can be configured at step 2568 to notify one or moreother waveguide systems of the mitigation scheme intended to be used forupdating one or more electromagnetic waves prior to executing the updateat step 2570. The notification can be sent wirelessly to one or moreother waveguide systems utilizing antennas if signal degradation in theelectromagnetic waves is too severe. If signal attenuation is tolerable,then the notification can be sent via the affected electromagneticwaves. In other embodiments, the waveguide system can be configured toskip step 2568 and perform the mitigation scheme using WMDM and/or FDMat step 2570 without notification. This embodiment can be applied incases where, for example, other recipient waveguide system(s) knowbeforehand what kind of mitigation scheme would be used, or therecipient waveguide system(s) are configured to use signal detectiontechniques to discover the mitigation scheme. Once the mitigation schemeusing WMDM and/or FDM has been initiated at step 2570, the waveguidesystem can continue to process received communication signals at steps2562 and 2564 as described earlier using the updated configuration ofthe electromagnetic waves.

At step 2566, the waveguide system can monitor if the obstruction isstill present. This determination can be performed by sending testsignals (e.g., electromagnetic surface waves in the original wave mode)to other waveguide system(s) and awaiting test results back from thewaveguide systems if the situation has improved, and/or by using otherobstruction detection techniques such as signal reflection testing basedon the sent test signals. Once the obstruction is determined to havebeen removed (e.g., the transmission medium becomes dry), the waveguidesystem can proceed to step 2572 and determine that a signal update wasperformed at step 2568 using WMDM and/or FDM as a mitigation technique.The waveguide system can then be configured to notify recipientwaveguide system(s) at step 2568 of the intent to restore transmissionsto the original wave mode, or bypass this step and proceed to step 2570where it restores transmissions to an original wave mode and assumes therecipient waveguide system(s) know the original wave modes andcorresponding transmission parameters, or can otherwise detect thischange.

A waveguide system can also be adapted to receive electromagnetic wavesconfigured for WMDM and/or FDM. For example, suppose that anelectromagnetic wave having a high bandwidth (e.g., 10 GHz) TM01 wavemode is propagating on an insulated conductor as shown in FIG. 31 andthat the electromagnetic wave is generated by a source waveguide system.At step 2582, a recipient waveguide system can be configured to processthe single electromagnetic wave with the TM01 wave mode under normalcondition. Suppose, however, that the source waveguide systemtransitions to transmitting electromagnetic waves using WMDM and FDMalong with a TM01 wave mode with a lower bandwidth on the insulatedconductor, as previously described in FIG. 31. In this instance, therecipient waveguide system would have to process multipleelectromagnetic waves of different wave modes. Specifically, therecipient waveguide system would be configured at step 2582 toselectively process each of the first through ninth electromagneticwaves using WMDM and FDM and the electromagnetic wave using the TM01wave mode as shown in FIG. 31.

Once the one or more electromagnetic waves have been received at step2582, the recipient waveguide can be configured to use signal processingtechniques to obtain the communication signals that were conveyed by theelectromagnetic wave(s) generated by the source waveguide system at step2564 (and/or step 2570 if an update has occurred). At step 2586, therecipient waveguide system can also determine if the source waveguidesystem has updated the transmission scheme. The update can be detectedfrom data provided in the electromagnetic waves transmitted by thesource waveguide system, or from wireless signals transmitted by thesource waveguide system. If there are no updates, the recipientwaveguide system can continue to receive and process electromagneticwaves at steps 2582 and 2584 as described before. If, however, an updateis detected at step 2586, the recipient waveguide system can proceed tostep 2588 to coordinate the update with the source waveguide system andthereafter receive and process updated electromagnetic waves at steps2582 and 2584 as described before.

It will be appreciated that method 2560 can be used in any communicationscheme including simplex and duplex communications between waveguidesystems. Accordingly, a source waveguide system that performs an updatefor transmitting electromagnetic waves according to other wave modeswill in turn cause a recipient waveguide system to perform similar stepsfor return electromagnetic wave transmissions. It will also beappreciated that the aforementioned embodiments associated with method2560 of FIG. 26 and the embodiments shown in FIGS. 27 through 32 can becombined in whole or in part with other embodiments of the subjectdisclosure for purposes of mitigating propagation losses caused by anobstruction at or in a vicinity of an outer surface of a transmissionmedium (e.g., insulated conductor, uninsulated conductor, or anytransmission medium having an external dielectric layer). Theobstruction can be a liquid (e.g., water), a solid object disposed onthe outer surface of the transmission medium (e.g., ice, snow, a splice,a tree limb, etc.), or any other objects located at or near the outersurface of the transmission medium.

While for purposes of simplicity of explanation, the respectiveprocesses are shown and described as a series of blocks in FIG. 26, itis to be understood and appreciated that the claimed subject matter isnot limited by the order of the blocks, as some blocks may occur indifferent orders and/or concurrently with other blocks from what isdepicted and described herein. Moreover, not all illustrated blocks maybe required to implement the methods described herein.

Referring now to FIGS. 33 and 34, block diagrams illustrating example,non-limiting embodiments for transmitting orthogonal wave modesaccording to the method 2560 of FIG. 26 are shown. FIG. 33 depicts anembodiment for simultaneously transmitting a TM00 wave mode, an HE11wave mode with vertical polarization, and an HE11 wave mode withhorizontal polarization as depicted in an instance in time in FIG. 27.In one embodiment, these orthogonal wave modes can be transmitted with awaveguide launcher having eight (8) MMICs as shown in FIG. 18K locatedat symmetrical locations (e.g., north, northeast, east, southeast,south, southwest, west, and northwest). The waveguide launcher of FIG.(or FIG. 18J) can also be configured with these 8 MMICs. Additionally,the waveguide launcher can be configured with a cylindrical sleeve 2523Aand tapered dielectric that wraps around the transmission medium (e.g.,insulated conductor, uninsulated conductor, or other cable with adielectric layer such as dielectric core). The housing assembly of thewaveguide launcher (not shown) can be configured to include a mechanism(e.g., a hinge) to enable a longitudinal opening of the waveguidelauncher for placement and latching around a circumference of atransmission medium.

With these configurations in mind, the waveguide launcher can includethree transmitters (TX1, TX2, and TX3) coupled to MMICs having variouscoordinate positions (see FIG. 25AG and FIG. 18W). The interconnectivitybetween the transmitters (TX1, TX2, and TX3) and the MMICs can beimplemented with a common printed circuit board or other suitableinterconnecting technology. The first transmitter (TX1) can beconfigured to launch a TM00 wave mode, the second transmitter (TX2) canbe configured to launch an HE11 vertical polarization wave mode, and thethird transmitter (TX3) can be configured to launch an HE11 horizontalpolarization wave mode.

A first signal port (shown as “SP1”) of the first transmitter (TX1) canbe coupled in parallel to each of the 8 MMICs. A second signal port(shown as “SP2”) of the first transmitter (TX1) can be coupled to aconductive sleeve 2523A that is placed on the transmission medium by thewaveguide launcher as noted above. The first transmitter (TX1) can beconfigured to receive a first group of the communication signalsdescribed in step 2562 of FIG. 26. The first group of communicationsignals can be frequency-shifted by the first transmitter (TX1) fromtheir native frequencies (if necessary) for an orderly placement of thecommunication signals in channels of a first electromagnetic waveconfigured according to the TM00 wave mode. The 8 MMICs coupled to thefirst transmitter (TX1) can be configured to up-convert (ordown-convert) the first group of the communication signals to the samecenter frequency (e.g., 1 GHz for the first electromagnetic wave asdescribed in relation to FIG. 31). All 8 MMICs would have synchronizedreference oscillators that can be phase locked using varioussynchronization techniques.

Since the 8 MMICs receive signals from the first signal port of thefirst transmitter (TX1) based on the reference provided by the secondsignal port, the 8 MMICs thereby receive signals with the same polarity.Consequently, once these signals have been up-converted (ordown-converted) and processed for transmission by the 8 MMICs, one ormore antennas of each of the 8 MMICs simultaneously radiates signalswith electric fields of the same polarity. Collectively, MMICs that areopposite in location to each other (e.g., MMIC north and MMIC south)will have an electric field structure aligned towards or away from thetransmission medium, thereby creating at a certain instance in time anoutward field structure like the TM00 wave mode shown in FIG. 27. Due tothe constant oscillatory nature of the signals radiated by the 8 MMICs,it will be appreciated that at other instances in time, the fieldstructure shown in FIG. 27 will radiate inward. By symmetricallyradiating electric fields with the same polarity the collection ofopposing MMICs contribute to the inducement of a first electromagneticwave having a TM00 wave mode that propagates on a transmission mediumwith a dielectric layer and can convey the first group of thecommunication signals to a receiving waveguide system.

Turning now to the second transmitter (TX2) in FIG. 33, this transmitterhas a first signal port (SP1) coupled to MMICs located in north,northeast and northwest positions, while a second signal port (SP2) ofthe second transmitter (TX2) is coupled to the MMICs located in south,southeast and southwest positions (see FIG. 18K). The second transmitter(TX2) can be configured to receive a second group of the communicationsignals described in step 2562 of FIG. 26, which differs from the firstgroup of the communication signals received by the first transmitter(TX1). The second group of communication signals can befrequency-shifted by the second transmitter (TX2) from their nativefrequencies (if necessary) for an orderly placement of the communicationsignals in channels of a second electromagnetic wave configuredaccording to an HE11 wave mode with vertical polarization. The 6 MMICscoupled to the second transmitter (TX2) can be configured to up-convert(or down-conversion) the second group of the communication signals tothe same center frequency as used for the TM00 wave mode (i.e., 1 GHz asdescribed in relation to FIG. 31). Since a TM00 wave mode is orthogonalto an HE11 wave mode with vertical polarization, they can share the samecenter frequency in an overlapping frequency band without interference.

Referring back to FIG. 33, the first signal port (SP1) of the secondtransmitter (TX2) generates signals of opposite polarity to the signalsof the second signal port (SP2). As a result, the electric fieldalignment of signals generated by one or more antennas of the northernMMIC will be of opposite polarity to the electric field alignment ofsignals generated by one or more antennas of the southern MMIC.Consequently, the electric fields of the north and south MMICs will havean electric field structure that is vertically aligned in the samedirection, thereby creating at a certain instance in time a northernfield structure like the HE11 wave mode with vertical polarization shownin FIG. 27. Due to the constant oscillatory nature of the signalsradiated by the north and south MMICs, it will be appreciated that atother instances in time, the HE11 wave mode will have a southern fieldstructure. Similarly, based on the opposite polarity of signals suppliedto the northeast and southeast MMICs by the first and second signalports, respectively, these MMICs will generate at a certain instance intime the curved electric field structure shown on the east side of theHE11 wave mode with vertical polarization depicted in FIG. 27. Also,based on the opposite polarity of signals supplied to the northwest andsouthwest MMICs, these MMICs will generate at a certain instance in timethe curved electric field structure shown on the west side of the HE11wave mode with vertical polarization depicted in FIG. 27.

By radiating electric fields with opposite polarity by opposing MMICs(north, northeast and northwest versus south, southeast and southwest),the collection of signals with a directionally aligned field structurecontribute to the inducement of a second electromagnetic wave having theHE11 wave mode with vertical polarization shown in FIG. 27. The secondelectromagnetic wave propagates along the “same” transmission medium aspreviously described for the first transmitter (TX1). Given theorthogonality of a TM00 wave mode and an HE11 wave mode with verticalpolarization, there will be ideally no interference between the firstelectromagnetic wave and the second electromagnetic wave. Consequently,the first and second electromagnetic waves having overlapping frequencybands propagating along the same transmission medium can successfullyconvey the first and second groups of the communication signals to thesame (or other) receiving waveguide system.

Turning now to the third transmitter (TX3) in FIG. 33, this transmitterhas a first signal port (SP1) coupled to MMICs located in east,northeast and southeast positions, while a second signal port (SP2) ofthe third transmitter (TX3) is coupled to the MMICs located in west,northwest and southwest positions (see FIG. 18K). The third transmitter(TX3) can be configured to receive a third group of the communicationsignals described in step 2562 of FIG. 26, which differs from the firstand second groups of the communication signals received by the firsttransmitter (TX1) and the second transmitter (TX2), respectively. Thethird group of communication signals can be frequency-shifted by thethird transmitter (TX3) from their native frequencies (if necessary) foran orderly placement of the communication signals in channels of asecond electromagnetic wave configured according to an HE11 wave modewith horizontal polarization. The 6 MMICs coupled to the thirdtransmitter (TX3) can be configured to up-convert (or down-conversion)the third group of the communication signals to the same centerfrequency as used for the TM00 wave mode and HE11 wave mode withvertical polarization (i.e., 1 GHz as described in relation to FIG. 31).Since a TM00 wave mode, an HE11 wave mode with vertical polarization,and an HE11 wave mode with horizontal polarization are orthogonal, theycan share the same center frequency in an overlapping frequency bandwithout interference.

Referring back to FIG. 33, the first signal port (SP1) of the thirdtransmitter (TX3) generates signals of opposite polarity to the signalsof the second signal port (SP2). As a result, the electric fieldalignment of signals generated by one or more antennas of the easternMMIC will be of opposite polarity to the electric field alignment ofsignals generated by one or more antennas of the western MMIC.Consequently, the electric fields of the east and west MMICs will havean electric field structure that is horizontally aligned in the samedirection, thereby creating at a certain instance in time a westernfield structure like the HE11 wave mode with horizontal polarizationshown in FIG. 27. Due to the constant oscillatory nature of the signalsradiated by the east and west MMICs, it will be appreciated that atother instances in time, the HE11 wave mode will have an eastern fieldstructure. Similarly, based on the opposite polarity of signals suppliedto the northeast and northwest MMICs by the first and second signalports, respectively, these MMICs will generate at a certain instance intime the curved electric field structure shown on the north side of theHE11 wave mode with horizontal polarization depicted in FIG. 27. Also,based on the opposite polarity of signals supplied to the southeast andsouthwest MMICs, these MMICs will generate at a certain instance in timethe curved electric field structure shown on the south side of the HE11wave mode with horizontal polarization depicted in FIG. 27.

By radiating electric fields with opposite polarity by opposing MMICs(east, northeast and southeast versus west, northwest and southwest),the collection of signals with a directionally aligned field structurecontribute to the inducement of a third electromagnetic wave having theHE11 wave mode with horizontal polarization shown in FIG. 27. The thirdelectromagnetic wave propagates along the “same” transmission medium aspreviously described for the first transmitter (TX1) and the secondtransmitter (TX2). Given the orthogonality of a TM00 wave mode, an HE11wave mode with vertical polarization, and an HE11 wave mode withhorizontal polarization, there will be, ideally, no interference betweenthe first electromagnetic wave, the second electromagnetic wave, and thethird electromagnetic wave. Consequently, the first, second and thirdelectromagnetic waves having overlapping frequency bands propagatingalong the same transmission medium can successfully convey the first,second and third groups of the communication signal to the same (orother) receiving waveguide system.

Because of the orthogonality of the electromagnetic waves describedabove, a recipient waveguide system can be configured to selectivelyretrieve the first electromagnetic wave having the TM00 wave mode, thesecond electromagnetic wave having the HE11 wave mode with verticalpolarization, and the third electromagnetic wave having the HE11 wavemode with horizontal polarization. After processing each of theseelectromagnetic waves, the recipient waveguide system can be furtherconfigured to obtain the first, second and third group of thecommunication signals conveyed by these waves. FIG. 34 illustrates ablock diagram for selectively receiving each of the first, second andthird electromagnetic waves.

Specifically, the first electromagnetic wave having the TM00 wave modecan be selectively received by a first receiver (RX1) shown in FIG. 34by taking the difference between the signals received by all 8 MMICs andthe signal reference provided by the metal sleeve 2523A as depicted inthe block diagram in FIG. 35. The second electromagnetic wave having theHE11 wave mode with vertical polarization can be selectively received bya second receiver (RX2) shown in FIG. 34 by taking the differencebetween the signals received by the MMICs located in north, northeastand northwest positions and the signals received by the MMICs located insouth, southeast and southwest positions as depicted in the blockdiagram in FIG. 36. The third electromagnetic wave having the HE11 wavemode with horizontal polarization can be selectively received by a thirdreceiver (RX3) shown in FIG. 34 by taking the difference between thesignals received by the MMICs located in east, northeast and southeastpositions and the signals received by the MMICs located in west,northwest and southwest positions as depicted in the block diagram inFIG. 37.

FIG. 38 illustrates a simplified functional block diagram of an MMIC.The MMIC can, for example, utilize a mixer coupled to a reference (TX)oscillator that shifts one of the communication signals supplied by oneof the signal ports (SP1 or SP2) of one of the transmitters (TX1, TX2 orTX3) to a desired center frequency in accordance with the configurationsshown in FIG. 33. For example, in the case of TX 1, the communicationsignal from SP1 is supplied to a transmit path of each of the MMICs(i.e., NE, NW, SE, SW, N, S, E, and W). In the case of TX2, thecommunication signal from SP1 is supplied to another transmit path ofthree MMICs (i.e., N, E, and NW). Note the transmit paths used by MMICsN, E and W for the communication signal supplied by SP1 of TX2 aredifferent from the transmit paths used by the MMICs for thecommunication signal supplied by SP1 of TX1. Similarly, thecommunication signal from SP2 of TX2 is supplied to another transmitpath of three other MMICs (i.e., S, SE, and SW). Again, the transmitpaths used by MMICs S, SE and SW for the communication signal suppliedby SP2 of TX2 are different from the transmit paths used by the MMICsfor the communication signals from SP1 of TX1, and SP1 of TX2. Lastly,in the case of TX3, the communication signal from SP1 is supplied to yetanother transmit path of three MMICs (i.e., E, NE, and SE). Note thetransmit paths used for MMICs E, NE, and SE for the communication signalfrom SP1 of TX3 are different from the transmit paths used by the MMICsfor the communication signals supplied by SP1 of TX1, SP1 of TX2, andSP2 of TX2. Similarly, the communication signal from SP2 of TX3 issupplied to another transmit path of three other MMICs (i.e., W, NW, andSW). Again, the transmit paths used by MMICs W, NW, and SW for thecommunication signal supplied by SP2 of TX3 are different from thetransmit paths used by the MMICs for the communication signals from SP1of TX1, SP1 of TX2, and SP2 of TX2, and SP1 of TX3.

Once the communication signals have been frequency-shifted by the mixershown in the transmit path, the frequency-shifted signal generated bythe mixer can then be filtered by a bandpass filter that removesspurious signals. The output of the bandpass filter in turn can beprovided to a power amplifier that couples to an antenna by way of aduplexer for radiating signals in the manner previously described. Theduplexer can be used to isolate a transmit path from a receive path. Theillustration of FIG. 38 is intentionally oversimplified to enable easeof illustration.

It will be appreciated that other components (not shown) such as animpedance matching circuit, phase lock loop, or other suitablecomponents for improving the accuracy and efficiency of the transmissionpath (and receive path) is contemplated by the subject disclosure.Furthermore, while a single antenna can be implemented by each MMIC,other designs with multiple antennas can likewise be employed. It isfurther appreciated that to achieve more than one orthogonal wave modewith overlapping frequency bands (e.g., TM00, HE11 Vertical, and HE11Horizontal wave modes described above), the transmit path can berepeated N times using the same reference oscillator. N can represent aninteger associated with the number of instances the MMIC is used togenerate each of the wave modes. For example, in FIG. 33, MMIC NE isused three times; hence, MMIC NE has three transmit paths (N=3), MMIC NWis used three times; hence, MMIC NW has three transmit paths (N=3), MMICN is used twice; hence, MMIC N has two transmit paths (N=2), and so on.If frequency division multiplexing is employed to generate the same wavemodes in other frequency band(s) (see FIGS. 31 and 32), the transmitpath can be further repeated using different reference oscillator(s)that are centered at the other frequency band(s).

In the receive path shown in FIG. 38, N signals supplied by N antennasvia the duplexer of each transmit path in the MMIC can be filtered by acorresponding N bandpass filters, which supply their output to Nlow-noise amplifiers. The N low-noise amplifiers in turn supply theirsignals to N mixers to generate N intermediate-frequency receivedsignals. As before, N is representative of the number of instances theMMIC is used for receiving wireless signals for different wave modes.For example, in FIG. 34, MMIC NE is used in three instances; hence, MMICNE has three receive paths (N=3), MMIC N is used in two instances;hence, MMIC N has two receive paths (N=2), and so on.

Referring back to FIG. 38, to reconstruct a wave mode signal, Y receivedsignals supplied by receiver paths of certain MMICs or a reference froma metal sleeve is subtracted from X received signals supplied by otherMMICs based on the configurations shown in FIGS. 35-37. For example, aTM00 signal is reconstructed by supplying the received signals of allMMICs (NE, NW, SE, SW, N, S, E, W) to the plus port of the summer (i.e.,X signals), while the reference signal from the metal sleeve is suppliedto the negative port of the summer (i.e., Y signal)—see FIG. 35. Thedifference between the X and Y signals results in the TM00 signal. Toreconstruct the HE11 Vertical signal, the received signals of MMICs N,NE, and NW are supplied to the plus port of the summer (i.e., Xsignals), while the received signals of MMICs S, SE, and SW are suppliedto the negative port of the summer (i.e., Y signals)—see FIG. 36. Thedifference between the X and Y signals results in the HE11 verticalsignal. Lastly, to reconstruct the HE11 Horizontal signal, the receivedsignals of MMICs E, NE, and SE are supplied to the plus port of thesummer (i.e., X signals), while the received signals of MMICs W, NW, andSW are supplied to the negative port of the summer (i.e., Y signals)—seeFIG. 37. The difference between the X and Y signals results in the HE11horizontal signal. Since there are three wave mode signals beingreconstructed, the block diagram of the summer with the X and Y signalsis repeated three times.

Each of these reconstructed signals is at intermediate frequencies.These intermediate-frequency signals are provided to receivers (RX1, RX2and RX3) which include circuitry (e.g., a DSP, A/D converter, etc.) forprocessing and to selectively obtain communication signals therefrom.Similar to the transmit paths, the reference oscillators of the threereceiver paths can be configured to be synchronized with phase lock looptechnology or other suitable synchronization technique. If frequencydivision multiplexing is employed for the same wave modes in otherfrequency band(s) (see FIGS. 31 and 32), the receiver paths can befurther repeated using a different reference oscillator that is centeredat the other frequency band(s).

It will be appreciated that other suitable designs that can serve asalternative embodiments to those shown in FIGS. 33-38 can be used fortransmitting and receiving orthogonal wave modes. For example, there canbe fewer or more MMICs than described above. In place of the MMICs, orin combination, slotted launchers as shown in FIGS. 18D-18E, 18G, and18I can be used. It is further appreciated that more or fewersophisticated functional components can be used for transmitting orreceiving orthogonal wave modes. Accordingly, other suitable designsand/or functional components are contemplated by the subject disclosurefor transmitting and receiving orthogonal wave modes.

Referring now to FIG. 39, a block diagram illustrating an example,non-limiting embodiment of a polyrod antenna 2600 for transmittingwireless signals is shown. The polyrod antenna 2600 can be one of anumber of polyrod antennas that are utilized in an antenna array, suchas array 1976 of FIG. 19F. The antenna array can facilitate or otherwiseenable beam steering which can include beam forming. The beam steeringcan be associated with communication signals, including voice, video,data, messaging, testing signals.

In one or more embodiments, the polyrod antenna 2600 can include a core2628 having a number of different regions or portions. The core 2628 canbe connected with a waveguide 2622 configured to confine anelectromagnetic wave at least in part within the core (e.g., in a firstregion of the core covered by the waveguide). In one embodiment (notshown), the waveguide 2622 can have an opening for accepting atransmission medium (e.g., a dielectric cable) or other couplingdevices. In another embodiment, the waveguide 2622 can have a generator,radiating element or other components therein that generateelectromagnetic waves for propagating along the core 2628.

In one embodiment, another region 2606 of the core 2628 (e.g., outsideof the waveguide 2622) is configured to reduce a propagation loss of anelectromagnetic wave as the electromagnetic wave propagates into thatregion, such as by having a non-tapered or otherwise uniform diameter ofthe core. The particular length and/or diameter of the region 2606 ofthe core 2628 can be selected to facilitate the reduction of propagationloss of the electromagnetic wave.

In one embodiment, another region 2612 of the core 2628 (e.g., thedistal portion or end of the core that is outside of the waveguide 2622)can be tapered and can facilitate transmitting a wireless signal, suchas based on the electromagnetic wave propagating along the core 2628.The particular length, diameter, and/or angle of taper of the region2612 of the core 2628 can be selected to facilitate transmitting of thewireless signals. In one embodiment, the tip or end 2675 of the region2612 can be truncated (as shown in FIG. 39) or pointed.

In one embodiment, the length and/or diameter of the core 2628 can beselected based on a wavelength of the electromagnetic wave that will bepropagating along the dielectric core. For example, a diameter ofgreater than ¼λ can be used for the region 2606.

In one embodiment, an inner surface of the waveguide 2622 can beconstructed from a metallic material or other materials that reflectelectromagnetic waves and thereby enables the waveguide 2622 to beconfigured to guide the electromagnetic wave towards the core 2628. Inone embodiment, the core 2628 can comprise a dielectric core (e.g., asdescribed herein) that extends to, or in proximity of, the inner surfaceof the waveguide 2622. In another embodiment, the dielectric core can besurrounded by cladding (such as shown in FIG. 18A), whereby the claddingextends to the inner surface of the waveguide 2622. In yet otherembodiments, the core 2628 can comprise an insulated conductor, wherethe insulation extends to the inner surface of the waveguide 2622. Inthis embodiment, the insulated conductor can be a power line, a coaxialcable, or other types of insulated conductors. In one example, thetapered outer shape may extend to the diameter of the metallic wire. Inanother example, the tapered outer shape may extend to and includetapering of the metallic wire. In yet another example, the metallic wiremay or may not continue beyond the tip 2675.

Referring to FIG. 40, an e-field distribution is illustrated for thepolyrod antenna 2600. As shown, the electromagnetic wave is confined orsubstantially confined within the waveguide 2622 and then propagatesalong the core 2628 until it is transmitted as a wireless signal fromthe region 2612 of the core.

Referring now to FIGS. 41 and 42, diagrams are shown illustrating anexample, non-limiting embodiment of a polyrod antenna array 2900 whichutilizes four polyrod antennas 2600 for transmitting wireless signals.In this example, the polyrod antenna array 2900 utilizes the samepolyrod antennas 2600, which are uniformly spaced apart, such as 0.8 cmon center. The particular type of polyrod antenna, the number of polyrodantennas, and/or the spacing in the array can be selected according tovarious factors, such as based on parameters of the wireless signalsand/or electromagnetic waves that are being utilized.

Referring now to FIG. 43A, a block diagram illustrating an example,non-limiting embodiment of a hollow horn antenna 3600 is shown. In oneembodiment, the hollow horn antenna 3600 can be used in an array. As anexample, hollow horn antenna 3600 can be made from Teflon® and/or caninclude a cylindrical V-band feed 3622 for generating a signal to bewirelessly transmitted. FIG. 43B illustrates an e-field distribution forthe hollow horn antenna 3600. As shown, the electromagnetic waves areconfined or substantially confined within the cylinder 3622.

Turning now to FIG. 44A, a block diagram illustrating an example,non-limiting embodiment of a communication system 4400 in accordancewith various aspects of the subject disclosure is shown. Thecommunication system 4400 can include a macro base station 4402 such asa base station or access point having antennas that covers one or moresectors (e.g., 6 or more sectors). The macro base station 4402 can becommunicatively coupled to a communication node 4404A that serves as amaster or distribution node for other communication nodes 4404B-Edistributed at differing geographic locations inside or beyond acoverage area of the macro base station 4402. The communication nodes4404 operate as a distributed antenna system configured to handlecommunications traffic associated with client devices such as mobiledevices (e.g., cell phones) and/or fixed/stationary devices (e.g., acommunication device in a residence, or commercial establishment) thatare wirelessly coupled to any of the communication nodes 4404. Inparticular, the wireless resources of the macro base station 4402 can bemade available to mobile devices by allowing and/or redirecting certainmobile and/or stationary devices to utilize the wireless resources of acommunication node 4404 in a communication range of the mobile orstationary devices.

The communication nodes 4404A-E can be communicatively coupled to eachother over an interface 4410. In one embodiment, the interface 4410 cancomprise a wired or tethered interface (e.g., fiber optic cable). Inother embodiments, the interface 4410 can comprise a wireless RFinterface forming a radio distributed antenna system. In variousembodiments, the communication nodes 4404A-E can include one or moreantennas, such as dielectric horn antennas or antenna arrays, poly rodantennas or antenna arrays or any of the other antennas describedherein. The communication nodes 4404A-E can be configured to providecommunication services to mobile and stationary devices according toinstructions provided by the macro base station 4402. In other examplesof operation however, the communication nodes 4404A-E operate merely asanalog repeaters to spread the coverage of the macro base station 4402throughout the entire range of the individual communication nodes4404A-E.

The micro base stations (depicted as communication nodes 4404) candiffer from the macro base station in several ways. For example, thecommunication range of the micro base stations can be smaller than thecommunication range of the macro base station. Consequently, the powerconsumed by the micro base stations can be less than the power consumedby the macro base station. The macro base station optionally directs themicro base stations as to which mobile and/or stationary devices theyare to communicate with, and which carrier frequency, spectralsegment(s) and/or timeslot schedule of such spectral segment(s) are tobe used by the micro base stations when communicating with certainmobile or stationary devices. In these cases, control of the micro basestations by the macro base station can be performed in a master-slaveconfiguration or other suitable control configurations. Whetheroperating independently or under the control of the macro base station4402, the resources of the micro base stations can be simpler and lesscostly than the resources utilized by the macro base station 4402.

Turning now to FIG. 44B, a block diagram illustrating an example,non-limiting embodiment of the communication nodes 4404B-E of thecommunication system 4400 of FIG. 44A is shown. In this illustration,the communication nodes 4404B-E are placed on a utility fixture such asa light post. In other embodiments, some of the communication nodes4404B-E can be placed on a building or a utility post or pole that isused for distributing power and/or communication lines. Thecommunication nodes 4404B-E in these illustrations can be configured tocommunicate with each other over the interface 4410, which in thisillustration is shown as a wireless interface. The communication nodes4404B-E can also be configured to communicate with mobile or stationarydevices 4406A-C over a wireless interface 4411 that conforms to one ormore communication protocols (e.g., fourth generation (4G) wirelesssignals such as LTE signals or other 4G signals, fifth generation (5G)wireless signals, WiMAX, 802.11 signals, ultra-wideband signals, etc.).The communication nodes 4404 can be configured to exchange signals overthe interface 4410 at an operating frequency that is may be higher(e.g., 28 GHz, 38 GHz, 60 GHz, 80 GHz or higher) than the operatingfrequency used for communicating with the mobile or stationary devices(e.g., 1.9 GHz) over interface 4411. The high carrier frequency and awider bandwidth can be used for communicating between the communicationnodes 4404 enabling the communication nodes 4404 to providecommunication services to multiple mobile or stationary devices via oneor more differing frequency bands, (e.g. a 900 MHz band, 1.9 GHz band, a2.4 GHz band, and/or a 5.8 GHz band, etc.) and/or one or more differingprotocols. In other embodiments, particularly where the interface 4410is implemented via a guided wave communications system on a wire, awideband spectrum in a lower frequency range (e.g. in the range of 2-6GHz, 4-10 GHz, etc.) can be employed.

Turning now to FIG. 44C, a block diagram illustrating an example,non-limiting embodiment of downlink and uplink communication techniquesfor enabling a base station to communicate with the communication nodes4404 of FIG. 44A is shown. In the illustrations of FIG. 44C, downlinksignals (i.e., signals directed from the macro base station 4402 to thecommunication nodes 4404) can be spectrally divided into controlchannels 4422, downlink spectral segments 4426 each including modulatedsignals which can be frequency converted to their original/nativefrequency band (e.g., cellular band, or other native frequency band) forenabling the communication nodes 4404 to communicate with one or moremobile or stationary devices 4426, and pilot signals 4424 which can besupplied with some or all of the spectral segments 4426 for mitigatingdistortion created between the communication nodes 4404. The pilotsignals 4424 can be processed by tethered or wireless transceivers ofdownstream communication nodes 4404 to remove distortion from a receivesignal (e.g., phase distortion). Each downlink spectral segment 4426 canbe allotted a bandwidth 4425 sufficiently wide (e.g., 50 MHz) to includea corresponding pilot signal 4424 and one or more downlink modulatedsignals located in frequency channels (or frequency slots) in thespectral segment 4426. The modulated signals can represent cellularchannels, WLAN channels or other modulated communication signals (e.g.,10-20 MHz), which can be used by the communication nodes 4404 forcommunicating with one or more mobile or stationary devices 4406.

Uplink modulated signals generated by mobile or stationary communicationdevices in their native/original frequency bands (e.g., cellular band,or other native frequency band) can be frequency converted and therebylocated in frequency channels (or frequency slots) in the uplinkspectral segment 4430. The uplink modulated signals can representcellular channels, WLAN channels or other modulated communicationsignals. Each uplink spectral segment 4430 can be allotted a similar orsame bandwidth 4425 to include a pilot signal 4428 which can be providedwith some or each spectral segment 4430 to enable upstream communicationnodes 4404 and/or the macro base station 4402 to remove distortion(e.g., phase error).

In the embodiment shown, the downlink and uplink spectral segments 4426and 4430 each comprise a plurality of frequency channels (or frequencyslots), which can be occupied with modulated signals that have beenfrequency converted from any number of native/original frequency bands(e.g. a 900 MHz band, 1.9 GHz band, a 2.4 GHz band, and/or a 5.8 GHzband, etc.). The modulated signals can be up-converted to adjacentfrequency channels in downlink and uplink spectral segments 4426 and4430. In this fashion, while some adjacent frequency channels in adownlink spectral segment 4426 can include modulated signals originallyin a same native/original frequency band, other adjacent frequencychannels in the downlink spectral segment 4426 can also includemodulated signals originally in different native/original frequencybands, but frequency converted to be located in adjacent frequencychannels of the downlink spectral segment 4426. For example, a firstmodulated signal in a 1.9 GHz band and a second modulated signal in thesame frequency band (i.e., 1.9 GHz) can be frequency converted andthereby positioned in adjacent frequency channels of a downlink spectralsegment 4426. In another illustration, a first modulated signal in a 1.9GHz band and a second communication signal in a different frequency band(i.e., 2.4 GHz) can be frequency converted and thereby positioned inadjacent frequency channels of a downlink spectral segment 4426.Accordingly, frequency channels of a downlink spectral segment 4426 canbe occupied with any combination of modulated signals of the same ordiffering signaling protocols and of a same or differing native/originalfrequency bands.

Similarly, while some adjacent frequency channels in an uplink spectralsegment 4430 can include modulated signals originally in a samefrequency band, adjacent frequency channels in the uplink spectralsegment 4430 can also include modulated signals originally in differentnative/original frequency bands, but frequency converted to be locatedin adjacent frequency channels of an uplink segment 4430. For example, afirst communication signal in a 2.4 GHz band and a second communicationsignal in the same frequency band (i.e., 2.4 GHz) can be frequencyconverted and thereby positioned in adjacent frequency channels of anuplink spectral segment 4430. In another illustration, a firstcommunication signal in a 1.9 GHz band and a second communication signalin a different frequency band (i.e., 2.4 GHz) can be frequency convertedand thereby positioned in adjacent frequency channels of the uplinkspectral segment 4426. Accordingly, frequency channels of an uplinkspectral segment 4430 can be occupied with any combination of modulatedsignals of a same or differing signaling protocols and of a same ordiffering native/original frequency bands. It should be noted that adownlink spectral segment 4426 and an uplink spectral segment 4430 canthemselves be adjacent to one another and separated by only a guard bandor otherwise separated by a larger frequency spacing, depending on thespectral allocation in place.

It will be appreciated that downlink modulated signals generated by abase station in their native/original frequency bands (e.g., cellularband, or other native frequency band) can be frequency shifted to one ofthe downlink spectral segments 4426 without re-modulating the modulatedsignals. That is, frequency shifting the downlink modulated signals caninclude transitioning the downlink modulated signals from itsnative/original frequency bands to a spectral segment 4426 withoutmodifying the signaling protocol (e.g., LTE, 5G, DOCSIS, etc.) and/orthe modulation technique (e.g., orthogonal frequency-division multipleaccess; generally, referred to as OFDMA, etc.) used by the base stationto generate the downlink modulated signal in its native/originalfrequency bands. Frequency shifting the downlink modulated signals inthis manner preserves the signaling protocol and/or modulation techniqueused to generate the downlink modulated signals, and thereby enables anyof the communication nodes 4404 to restore the downlink modulatedsignals in spectral segment 4426 to its respective native/originalfrequency bands with only a frequency conversion process.

Similarly, uplink modulated signals generated by mobile or stationarycommunication devices in their native/original frequency bands (e.g.,cellular band, or other native frequency band) can be frequency shiftedto one of the uplink spectral segments 4430 without re-modulating themodulated signals. That is, frequency shifting the uplink modulatedsignals can include transitioning the uplink modulated signals from itsnative/original frequency bands to a spectral segment 4430 withoutmodifying the signaling protocol (e.g., LTE, 5G, DOCSIS, etc.) and/orthe modulation technique (e.g., single carrier frequency-divisionmultiple access; generally, referred to as SC-FDMA, etc.) used by themobile or stationary communication devices to generate the uplinkmodulated signal in its native/original frequency bands. Frequencyshifting the uplink modulated signals in this manner preserves thesignaling protocol and/or modulation technique used to generate theuplink modulated signals, and thereby enables any of the communicationnodes 4404 to restore the uplink modulated signals in spectral segment4430 to its respective native/original frequency bands with only afrequency conversion process.

The foregoing frequency conversion processes can correspond to afrequency up-conversion, a frequency down-conversion, or a combinationthereof. The frequency conversion process can be performed with analogcircuitry (e.g., amplifiers, mixers, filters, etc.) without digitalconversion, which can simplify the design requirements of thecommunication nodes 4404. Frequency conversion can be also performed viadigital signal processing while preserving the signaling protocol and/ormodulation technique, for example, by shifting the signals in thefrequency domain. It will be appreciated that the foregoing principlesof frequency conversion without modifying the signaling protocol and/orthe modulation technique of previously modulated signals itsnative/original frequency bands can be applied to any embodiments of thesubject disclosure including without limitation wireless signalspropagating in free space between antenna systems of a distributedantenna system, and/or guided electromagnetic waves that propagate alonga physical transmission medium.

Turning now to FIG. 44D, a graphical diagram 4460 illustrating anexample, non-limiting embodiment of a frequency spectrum is shown. Inparticular, a spectrum 4462 is shown for a distributed antenna systemthat conveys modulated signals occupying frequency channels of uplink ordownlink spectral segments after they have been converted in frequency(e.g. via up-conversion or down-conversion) from one or moreoriginal/native spectral segments into the spectrum 4462.

As previously discussed two or more different communication protocolscan be employed to communicate upstream and downstream data. When two ormore differing protocols are employed, a first subset of the downlinkfrequency channels of a downlink spectral segment 4426 can be occupiedby frequency converted modulated signals in accordance with a firststandard protocol and a second subset of the downlink frequency channelsof the same or a different downlink spectral segment 4430 can beoccupied by frequency converted modulated signals in accordance with asecond standard protocol that differs from the first standard protocol.Likewise a first subset of the uplink frequency channels of an uplinkspectral segment 4430 can be received by the system for demodulation inaccordance with the first standard protocol and a second subset of theuplink frequency channels of the same or a different uplink spectralsegment 4430 can be received in accordance with a second standardprotocol for demodulation in accordance with the second standardprotocol that differs from the first standard protocol.

In the example shown, the downstream channel band 4444 includes a firstplurality of downstream spectral segments represented by separatespectral shapes of a first type representing the use of a firstcommunication protocol. The downstream channel band 4444′ includes asecond plurality of downstream spectral segments represented by separatespectral shapes of a second type representing the use of a secondcommunication protocol. Likewise the upstream channel band 4446 includesa first plurality of upstream spectral segments represented by separatespectral shapes of the first type representing the use of the firstcommunication protocol. The upstream channel band 4446′ includes asecond plurality of upstream spectral segments represented by separatespectral shapes of the second type representing the use of the secondcommunication protocol. These separate spectral shapes are meant to beplaceholders for the frequency allocation of each individual spectralsegment along with associated reference signals, control channels and/orclock signals. While the individual channel bandwidth is shown as beingroughly the same for channels of the first and second type, it should benoted that upstream and downstream channel bands 4444, 4444′, 4446 and4446′ may be of differing bandwidths. Additionally, the spectralsegments in these channel bands of the first and second type may be ofdiffering bandwidths, depending on available spectrum and/or thecommunication standards employed.

Turning now to FIG. 44E, a graphical diagram 4470 illustrating anexample, non-limiting embodiment of a frequency spectrum is shown. Inparticular a portion of the spectrum 4462 of FIG. 44D is shown for adistributed antenna system that conveys modulated signals in the form ofchannel signals that have been converted in frequency (e.g. viaup-conversion or down-conversion) from one or more original/nativespectral segments.

The portion 4472 includes a portion of a downlink or uplink spectralsegment 4426 and 4430 that is represented by a spectral shape and thatrepresents a portion of the bandwidth set aside for a control channel,reference signal, and/or clock signal. The spectral shape 4474, forexample, represents a control channel that is separate from referencesignal 4479 and a clock signal 4478. It should be noted that the clocksignal 4478 is shown with a spectral shape representing a sinusoidalsignal that may require conditioning into the form of a more traditionalclock signal. In other embodiments however, a traditional clock signalcould be sent as a modulated carrier wave such by modulating thereference signal 4479 via amplitude modulation or other modulationtechnique that preserves the phase of the carrier for use as a phasereference. In other embodiments, the clock signal could be transmittedby modulating another carrier wave or as another signal. Further, it isnoted that both the clock signal 4478 and the reference signal 4479 areshown as being outside the frequency band of the control channel 4474.

In another example, the portion 4475 includes a portion of a downlink oruplink spectral segment 4426 and 4430 that is represented by a portionof a spectral shape that represents a portion of the bandwidth set asidefor a control channel, reference signal, and/or clock signal. Thespectral shape 4476 represents a control channel having instructionsthat include digital data that modulates the reference signal, viaamplitude modulation, amplitude shift keying or other modulationtechnique that preserves the phase of the carrier for use as a phasereference. The clock signal 4478 is shown as being outside the frequencyband of the spectral shape 4476. The reference signal, being modulatedby the control channel instructions, is in effect a subcarrier of thecontrol channel and is in-band to the control channel. Again, the clocksignal 4478 is shown with a spectral shape representing a sinusoidalsignal, in other embodiments however, a traditional clock signal couldbe sent as a modulated carrier wave or other signal. In this case, theinstructions of the control channel can be used to modulate the clocksignal 4478 instead of the reference signal.

Consider the following example, where the control channel 4476 iscarried via modulation of a reference signal in the form of a continuouswave (CW) from which the phase distortion in the receiver is correctedduring frequency conversion of the downlink or uplink spectral segment4426 and 4430 back to its original/native spectral segment. The controlchannel 4476 can be modulated with a robust modulation such as pulseamplitude modulation, binary phase shift keying, amplitude shift keyingor other modulation scheme to carry instructions between networkelements of the distributed antenna system such as network operations,administration and management traffic and other control data. In variousembodiments, the control data can include without limitation:

-   -   Status information that indicates online status, offline status,        and network performance parameters of each network element.    -   Network device information such as module names and addresses,        hardware and software versions, device capabilities, etc.    -   Spectral information such as frequency conversion factors,        channel spacing, guard bands, uplink/downlink allocations,        uplink and downlink channel selections, etc.    -   Environmental measurements such as weather conditions, image        data, power outage information, line of sight blockages, etc.

In a further example, the control channel data can be sent viaultra-wideband (UWB) signaling. The control channel data can betransmitted by generating radio energy at specific time intervals andoccupying a larger bandwidth, via pulse-position or time modulation, byencoding the polarity or amplitude of the UWB pulses and/or by usingorthogonal pulses. In particular, UWB pulses can be sent sporadically atrelatively low pulse rates to support time or position modulation, butcan also be sent at rates up to the inverse of the UWB pulse bandwidth.In this fashion, the control channel can be spread over an UWB spectrumwith relatively low power, and without interfering with CW transmissionsof the reference signal and/or clock signal that may occupy in-bandportions of the UWB spectrum of the control channel.

In one or more embodiments, communication device 4510 can include anantenna array 4515 for transmitting wireless signals. In one or moreembodiments, the antenna array 4515 can perform beam steering. Forexample, the antenna array 4515 can utilize a first subset of antennasof the antenna array to transmit first wireless signals 4525 directed(as shown by reference number 4527) via beam steering towards thecommunication device 4550. A second subset of antennas of the antennaarray 4515 can transmit second wireless signals 4530 directed (as shownby reference number 4532) via the beam steering towards a transmissionmedium 4575 (e.g., a power line connected between the utility poles4520, 4560). In one or more embodiments, the aforementioned beams can besimultaneously created by the same set of antennas in arrays 4510 and4550. In one or more embodiments, the beam steering can enable theantenna array to communicate with more than one wireless receiver withor without directing wireless signals to a transmission medium. In oneor more embodiments, the beam steering can enable the antenna array todirect the wireless signals to more than one transmission medium with orwithout communicating with a wireless receiver.

The first and second wireless signals 4525, 4530 can be associated withcommunication signals that are to be transmitted over the network. Forinstance, the first and second wireless signals 4525, 4530 can be thesame signals. In another example, the first wireless signals 4525 canrepresent a first subset of the communication signals, while the secondwireless signals 4530 represent a second subset of the communicationsignals. In one embodiment, the first and second wireless signals 4525,4530 can be different and can be based on interleaving of a group ofcommunication signals, such as video packets, and so forth. Thecommunication signals can be various types of signals includinginformation associated with subscriber services, network control,testing, and so forth.

In one or more embodiments, the second wireless signals 4530 induceelectromagnetic waves 4540. For example, the electromagnetic waves 4540are induced at a physical interface of the transmission medium 4575 andpropagate (as shown by reference number 4542) without requiring anelectrical return path. The electromagnetic waves 4540 are guided by thetransmission medium 4575 towards the communication device 4550, which ispositioned in proximity to the transmission medium. The electromagneticwaves 4540 can be representative of the second wireless signals 4530which are associated with the communication signals.

In one or more embodiments, the communication device 4550 can include areceiver that is configured to receive the electromagnetic waves 4540that are propagating along the transmission medium 4575. Various typesof receivers can be used for receiving the electromagnetic waves 4540,such as devices shown in FIGS. 7, 8 and 9A. System 4500 enables thecommunication device 4510 to transmit information which is received bythe communication device 4550 (e.g., another antenna array 4555) via thewireless communication path 4527 and via being guided by thetransmission medium 4575.

In one or more embodiments, the antenna arrays 4515, 4555 can includepolyrod antennas. For example, each of the polyrod antennas can includea core that is connected with a waveguide that is configured to confinean electromagnetic wave at least in part within the core in a particularregion of the core. In one embodiment, each of the polyrod antennas caninclude a core having a first region, a second region, a third region,and a fourth region, where the core comprises an interface in the firstregion. One of the plurality of transmitters can generate a firstelectromagnetic wave that induces a second electromagnetic wave at theinterface of the first region. The core can be connected with awaveguide that is configured to confine the second electromagnetic waveat least in part within the core in the first region, where the secondregion of the core is configured to reduce a radiation loss of thesecond electromagnetic wave as the second electromagnetic wavepropagates into the second region. The third region of the core can beconfigured to reduce a propagation loss of the second electromagneticwave as the second electromagnetic wave propagates into the thirdregion. The fourth region of the core can be outside of the waveguideand can be tapered to facilitate transmitting one of the first or secondwireless signals based on the second electromagnetic wave.

In one or more embodiments, the communication device 4510 can provide aphase adjustment to the second wireless signals 4530 to accomplish beamsteering towards the transmission medium 4575. FIG. 45 illustrates theantenna array 4555 and the receiver 4565 being co-located atcommunication device 4550, however, in another embodiment the antennaarray 4555 and the receiver 4565 can be separate devices that may or maynot be in proximity to each other. For example, the first wirelesssignals 4525 can be received by the antenna array 4555 of thecommunication device 4550 while the electromagnetic waves 4540 can bereceived by a receiver of a different communication device (not shown)that is in proximity to the transmission medium 4575.

FIGS. 46A, 46B, 46C, 46D, 46E, 46F, 46G, 46H, and 46I are graphicaldiagrams illustrating example, components of an inductive power supplyand graphical plots in accordance with various aspects described herein.FIG. 46A depicts a wire 4604 that carries an alternating current(hereinafter “AC wire” 4604) that generates a varying magnetic field4602. The magnetic field 4602, B, is usually weak. FIG. 46B depicts theAC wire 4604 with a magnetic core 4606 surrounding a section of the ACwire 4604. The magnetic field 4602 of the AC wire 4604 can besubstantially enhanced by the magnetic core 4606 (depicted in FIG. 46Cas magnetic field 4602′). The magnetic core 4606 can be constructed ofmaterials such as iron, nickel, or high permeability materials. Themagnetic field in the core 4606 can be characterized by its flux. Thoseskilled in the art will know how to calculate the flux of the magneticfield based on the characteristics of the core and the current flowingthrough the wire 4604. Generally, the flux increases as the currentincreases. With a high-permeability core, the magnetic field is almostentirely inside the magnetic core.

Magnetic materials for magnetic cores typically exhibit a phenomenonknown as “saturation”. As a consequence of saturation, there is amaximum usable magnetic flux (hereinafter: maximum flux, or Φ_(max))beyond which the advantageous magnetic properties of the material aredegraded. One such advantageous property is the core's ability of beingmagnetized and demagnetized without excessive heating (energy loss).Energy loss in a magnetic core increases dramatically as the coreapproaches saturation. The value of the maximum flux, when a core isused in a specific system, depends on the magnetic properties of thematerial and on system parameters such as an acceptable energy loss. Itis well known in the art how to determine a maximum flux based on theseand other system parameters. Maximum flux is typically less than thesaturated flux.

FIG. 46D depicts an exemplary plot of a possible alternating current4608 flowing through the AC wire 4604. The current produces acorresponding magnetic flux 4610 in the core 4606. The alternatingcurrent 4608 and the magnetic flux 4610 are in phase as depicted byvertical dashed line 4612. In certain situations, the peak of theinduced magnetic flux Φ₀ 4610 is substantially less than Φ_(max).

As illustrated in FIG. 46E, in certain applications it is necessary tosplit the core 4606 into two pieces 4606′ and 4606″ to make it possibleto mount it around the AC wire 4604. In such applications, anunavoidable gap 4612 remains between the two core pieces 4606′ and 4606″after they are mounted on the AC wire 4604. The presence of the gap 4612reduces the induced magnetic flux 4610 shown earlier in FIG. 46D.

One or more loops (aka turns) of an electrical wire can be wound aroundthe core 4606 as shown in FIG. 46F. The figure depicts only one turn,but those skilled in the art will know that one or more turns can beused to produce a desirable voltage output. The one or more turns ofconductor is commonly referred to as a “winding”, depicted in the figureas winding 4614. The varying magnetic field 4602′ in the core 4606induces a voltage 4616 across the two ends of the winding 4614. FIG. 46Gillustrates a plot that shows the alternating current 4608, the magneticflux 4610, and the induced voltage 4616 at the ends of the winding 4614.The induced voltage 4616 is 90° out of phase relative to the alternatingcurrent 4608 and the alternating flux 4610 (see vertical dashed line4618) because the voltage is proportional to the derivative of themagnetic flux (due to Faraday's law). For illustration purposes only, inorder to enhance clarity, the reference direction for the magnetic flux4610 has been chosen such that the polarity of the flux 4610 is the sameas the polarity of the alternating current 4608.

Energy is harvested by connecting a load 4620 to the winding 4614 asshown in FIG. 46H. The combination of the core 4606 and winding 4614coupled to the AC wire 4604 serves as an inductive power supply thatfacilitates supplying power to the load 4620. The load 4620 can compriseactive components, passive components, or a combination thereof. Forillustration purposes only, the load 4620 will be assumed to be aresistive load, such as a resistor. As illustrated in FIG. 46I, when aresistive load is connected to the winding 4614, it closes the windingcircuit, and current I₁ 4622 flows through the load 4620. However, thevoltage V₁ 4621 that appears across the load 4620 is of lower amplitudethan the open-circuit voltage V₀ 4616 (shown previously in FIG. 46G).The phase shift of the voltage is also reduced. The current I₁ 4622 thatflows through the load 4620 and through the winding 4614, when combinedwith the alternating current 4608 flowing on the AC wire 4604, has theeffect of reducing the total current I_(tot) 4623 that flows through thecore 4606. As a consequence, the magnetic flux Φ₁ 4610′ in the core 4606is also reduced, compared to the magnetic flux Φ₀ 4610 present underopen-circuit conditions (see FIG. 46G). To enable the inductive powersupply of FIG. 46H to provide more power to the load 4620, it would beuseful to enhance the magnetic flux 4610′ to make it approach Φ_(max) soas to improve the effectiveness of the magnetic core 4606.

FIG. 46J illustrates an embodiment for increasing the magnetic flux4610′ to approach Φ_(max) by connecting a capacitor 4624 in parallelwith the winding 4614. The combination of the capacitance of thecapacitor 4624 and the inductance of the winding 4614 can be configuredto form a resonant circuit. The frequency of resonance is 1/√{squareroot over (LC)}, where L is the inductance of the winding 4614 and C isthe capacitance of the capacitor 4624. If the frequency of resonance isclose to the frequency of the alternating current I₀ 4608, the magneticflux Φ₁ 4610′ through the core 4606 is enhanced. There are, however,problems with this method for enhancing the magnetic flux: a) therequirement that the frequency of resonance be close to the frequency ofthe alternating current means that the inductance of the winding 4614must be known with good precision, and the capacitance of the capacitor4624 must also be set with precision. This is especially difficult ifthe core 4606 has a gap 4613 as shown in FIG. 46E, because the gap 4613makes it difficult to predict inductance; b) capacitors suitable forresonance are bulky and expensive; c) it is difficult to adjust thevalues of L and C to achieve a precise amount of flux enhancement, withthe result that the enhanced flux might exceed Φ_(max) by a wide margin,or it might fall short; d) if the frequency of the alternating currentI₀ 4608 is not precisely known and stable, the amount of enhancementwill vary as the frequency changes. Accordingly, it would be desirableto have a way of enhancing the magnetic flux Φ₁ 4610′ through the core4606 that does not suffer from these problems and regulates the magneticflux accurately, such that the range of the magnetic flux approximates adesired range.

FIG. 46K illustrates a voltage waveform generator 4626 coupled to thewinding 4614, which overcomes the limitations of the embodiment shown inFIG. 46J. The voltage waveform generator 4626 is capable of generating adesired voltage waveform, which can be applied to the winding 4614.Faraday's law states that there is a relationship between a voltage,V(t), applied to winding 4614, and the magnetic flux Φ(t) 4610′. Inparticular, Faraday's law states the following formula dΦ(t)/dt=−V(t).Because of Faraday's law, the application of a voltage waveform to thewinding 4614 forces the magnetic flux 4610′ to have a time variationthat is defined by the voltage waveform. The voltage waveform can bedevised to regulate the magnetic flux 4610′ such that it varies between−Φ_(max) and +Φ_(max), and the variations can be adjusted to besynchronized to the alternating current 4608 so as to achieve effectiveenergy harvesting as depicted in FIG. 46L.

FIG. 46L shows the voltage waveform V(t) 4630, which goes positive andnegative synchronously with the alternating current I₀ 4608 flowingthrough the AC wire 4604. When the voltage waveform V(t) 4630 ispositive, the area 4628 below the voltage waveform 4630 is equal to2·Φ_(max). Therefore, because of Faraday's law, the magnetic flux 4610″swings from −Φ_(max) to Φ_(max) when the voltage waveform 4630 ispositive. When the voltage waveform V(t) 4630 is negative, the magneticflux 4610″ swings from −Φ_(max) to −Φ_(max). The magnetic flux 4610″which is generated in response to the voltage waveform 4630 supplied tothe winding 4614 is a significant improvement over the magnetic flux Φ₁4610′ illustrated in FIG. 46L as dotted lines (also previously shown inFIG. 46I).

The total current flowing through the core 4606 is the sum of thealternating current 4608 flowing through the AC wire 4604 and thecurrent flowing through the winding 4614. The total current flowingthrough the core 4606 exhibits the same time waveform as the magneticflux 4610″. During the time interval labeled “charge”, energy flows fromthe magnetic field in the core 4606 into the voltage waveform generator4626. During the time interval labeled “discharge”, energy flows out ofthe voltage waveform generator 4626 as the magnetic field flow in thecore 4606 becomes reversed. The plots show that the current, I_(charge),that flows into the voltage waveform generator 4626 during the “charge”time interval is larger than the current, I_(discharge), that flows outof the voltage waveform generator 4626 during the “discharge” timeinterval. Consequently, there is a net average flow of energy into thevoltage waveform generator 4626, as desired for achieving energyharvesting.

It will be appreciated that other waveforms can be generated by thevoltage waveform generator 4626 to regulate a magnetic flux 4610″ in thecore 4606 that approaches Φ_(max). For example, the positive andnegative square portions of the voltage waveform 4630 can be replacedwith positive and negative lobes of a sinusoid to achieve similarresults. Those skilled in the art will also appreciate that non-periodicwaveforms can be effective for energy harvesting; for example, thevoltage waveform generator might generate positive and negative lobes atirregular intervals in response to varying needs for harvested power, asdictated by power requirements of the load. Also, the shape, size, andduration of the positive and negative lobes can be adjusted to achieve aperiodic or non-periodic waveform; for example, a lobe such as area 4628might comprise a plurality of rectangular voltage swings whose rate andduration is adjusted adaptively to implement so-called Pulse-WidthModulation (PWM) for the purpose of dynamically adjusting the amount ofharvested energy. Accordingly, other waveforms generated by the voltagewaveform generator 4626 are contemplated by the subject disclosure.

FIG. 46M depicts an embodiment for implementing the voltage waveformgenerator 4626 of FIG. 46K. In this embodiment, the voltage waveformgenerator 4626 can comprise a plurality of switches 4640, 4642, 4644,and 4646 (also labeled as switches SW1-SW4) coupled to a storage device4624. The storage device 4624 can be a rechargeable battery, acapacitor, or any other suitable device that can store energy anddischarge energy. The winding 4614 can be connected the storage devicein different ways; for example, it can be connected with one polarity orwith the opposite polarity. It can also be disconnected from the storagedevice, and it can be shorted or opened. Such connection variations canbe achieved according to configurations of the plurality of switches4640, 4642, 4644, and 4646.

The positive part of the voltage waveform 4630 shown in FIG. 46L can beaccomplished by closing switches 4640 (SW1) and 4646 (SW4), and openingswitches 4642 (SW2) and 4644 (SW3). The negative part of the voltagewaveform 4630 can be accomplished by closing switches 4642 (SW2) and4644 (SW3), and opening switches 4640 (SW1) and 4646 (SW4). The part ofthe voltage waveform 4630 where the voltage is zero is accomplished byclosing switches 4640 (SW1) and 4644 (SW3), and opening switches 4642(SW2) and 4646 (SW4) (or, equivalently, by closing switches 4642 (SW2)and 4646 (SW4), and opening switches 4640 (SW1) and 4644 (SW3)). It willbe appreciated that other implementations of the voltage waveformgenerator 4626 can be used to regulate a magnetic flux 4610″ in the core4606 that approaches Φ_(max).

It will be further appreciated that the storage device 4624 can becharged to a desirable state prior to initiating the process ofgenerating the voltage waveform 4630. To accomplish this, the storagedevice 4624 in one embodiment can be pre-charged. In other embodiments,the storage device 4624 can be charged by energy harvested from themagnetic flux Φ₁ 4610′ prior to being enhanced by the voltage waveform4630 into magnetic flux 4610″. A stored-energy sensor (not shown) can becoupled to the storage device 4624 to measure a voltage chargeaccumulating in the storage device 4624. When the voltage charge exceedsa desirable threshold, the sensor can trigger the voltage waveformgenerator 4626 to initiate generation of the voltage waveform 4630. Thevoltage waveform 4630 thereafter causes a further charging of thestorage device 4624 as previously described in relation to the plot ofFIG. 46L.

It will also be appreciated that a processing circuit can be coupled tothe plurality of switches 4640, 4642, 4644, and 4646 via general purposeinput/output lines to selectively enable and disable these switches aspreviously described to generate the voltage waveform 4630. Theprocessing circuit can be a microprocessor, application specificintegrated circuit (ASIC), or other computing device suitable forperforming the operations described below. The processing circuit canalso be coupled to other sensor circuitry to measure the frequency andphase of the alternating current 4608 to generate a voltage waveform4630 that approximates the frequency and phase of the alternatingcurrent 4608 in order to increase the magnetic flux as close as possibleto Φ_(max). It will be further appreciated that the processing circuitcan be coupled to additional sensor circuitry that measures the magneticflux 4610″ to make sure that it does not exceed Φ_(max).

It will also be appreciated that the winding 4614 shown in FIGS. 46K and46M can be coupled to a passive and/or active load. The load cancorrespond to a device that requires energy to power circuitry in thedevice. In an alternative embodiment, a second winding (not shown) canbe added to the core 4606. The device can be, for example, a waveguidesystem such as described in the subject disclosure, or other device thatcan benefit from harvesting energy from the winding 4614. The winding4614 can be treated as a first winding coupled to the voltage waveformgenerator 4626 for enhancing the magnetic flux 4610″ in the core 4606,while the second winding can be used by a device to harvest energy fromthe second winding to power the device. The device can be, for example,a waveguide system such as described in the subject disclosure, or otherdevice that can benefit from harvesting energy from the second winding.

It will also be appreciated that the switches 4640, 4642, 4644, and 4646can be realized in a variety of ways. For example, in many embodiments,any one of switches can be realized via a semiconductor device such as atransistor, a FET, a thyristor, a TRIAC, a DIAC, or a diode or anothertype of semiconductor device. Other types of devices are also possible.It will be further appreciated that, although the switches are depictedas switching between open and closed conditions, implementations arepossible wherein one or more of the switches behave as proportionaldevices and operate in conditions that are intermediate between fullyopen and fully closed, as might be the case with semiconductor devicesoperated in an analog circuit. It will be further appreciated that otherimplementations of a voltage waveform generator are possible, as is wellknown in the art. For example, a voltage waveform generator might beimplemented as an analog amplifier operating in so-called class A, or B,or C, or D, as is well known in the art.

FIG. 46N illustrates a flow diagram of an example, non-limitingembodiment of a method 4650 for enhancing a magnetic flux in a core ofan inductive power supply in accordance with various aspects describedherein. Method 4650 can begin with step 4652 where a voltage waveformgenerator is configured to generate an alternating voltage waveform byselectively connecting a storage device to a winding of a magnetic core.At step 4654 the alternating magnetic flux in the core is increasedresponsive to the alternating voltage waveform applied to the winding.

Method 4650 provides several advantages over prior art systems. Forexample, method 4650 can be implemented without a resonant circuit thatrequires precise inductive and capacitive components. Method 4650 canalso be used to improve the performance of a split core. Additionally,method 4650 can be used by a designer to avoid resorting to a physicallylarger core to compensate for a low magnetic flux in the core.

FIG. 46O is a graphical diagram illustrating an example, animplementation of a voltage waveform generator to enhance a magneticflux in a core of an inductive power supply in accordance with variousaspects described herein. In the illustration of FIG. 46O, diodes 4641are shown connected across switches 4640, 4642, 4644, 4646 and 4647. Thediodes 4641 can be an integral component of each of the switches 4640,4642, 4644, 4646, and 4647, can be connected to the switches 4640, 4642,4644, 4646, and 4647 as external components, or a combination thereof. Aprocessing circuit (not shown) can be coupled to the switches 4640,4642, 4644, 4646, and 4647 as previously described via input/outputlines which can selectively enable or disable the switches 4640, 4642,4644, 4646, and 4647. When the processing circuit is not active andtherefore not controlling the switches 4640, 4642, 4644, 4646 and 4647via the input/output lines, the switches 4640, 4642, 4644, 4646, and4647 can be configured to be in an open state. In this configuration,only the diodes 4641 provide a means for connectivity between thewinding 4614 and the storage device 4624.

FIG. 46P illustrates a flow diagram of, an example, non-limitingembodiment of a method 4660 for enhancing a magnetic flux in a core ofan inductive power supply in accordance with various aspects describedherein. As noted above, the switches 4640, 4642, 4644, and 4646 can beconfigured in an open switch (“off”) state when the processing circuitis not receiving sufficient power from the windings 4614 of the magneticcore 4606 and the input/output lines of the processing circuit are notproviding a bias to the switches 4640, 4642, 4644, and 4646. In the“off” state the configuration of diodes 4641 connected to the switches4640, 4642, 4644, and 4646 can provide a means for the capacitor 4624(storage device) to gradually gain a charge as terminals 4614A and 4614Bof the windings 4614 alternate in polarity responsive to an alternatingcurrent flowing through the wire 4604.

For example, if terminal 4614A of the windings 4614 has a positivecharge, while terminal 4614B of the windings 4614 has a negative charge,the diodes 4641 of switches 4640 (SW1) and 4646 (SW4) will be forwardbiased, while the diodes 4641 of switches 4642 (SW2) and 4644 (SW3) willbe reversed biased. In this configuration, the positive terminal of thecapacitor 4624 will connect to terminal 4614A of the windings 4614 viathe diode 4641 of switch 4640 (SW1), while the negative terminal of thecapacitor 4624 will connect to terminal 4614B of the windings 4614 viathe diode 4641 of switch 4646 (SW4) enabling the capacitor 4624 to becharged. Similarly, when the alternating current flowing through thewire 4604 causes the windings 4614 to change the polarity of terminal4614A to a negative charge, and terminal 4614B to a positive charge, thediodes 4641 of switches 4640 (SW1) and 4646 (SW4) will be reversedbiased, while the diodes 4641 of switches 4642 (SW2) and 4644 (SW3) willbe forward biased. In this configuration, the positive terminal of thecapacitor 4624 will connect to terminal 4614B of the windings 4614 viathe diode 4641 of switch 4644 (SW3), while the negative terminal of thecapacitor 4624 will connect to terminal 4614A of the windings 4614 viathe diode 4641 of switch 4642 (SW2) enabling the capacitor 4624 tocontinue to gain a charge. As the alternating current flowing throughthe wire 4604 continues to alternate, the windings 4614 will graduallycharge the capacitor 4624.

The capacitor 4624, which serves as an energy storage device, can becoupled to the processing circuit as a power supply source. Once thecapacitor 4624 has gained sufficient energy it can power up theprocessing circuit at step 4662. The processing circuit can include apower regulation circuit which can indicate to the processing circuitwhether there is sufficient energy to perform functions such as sensingan amplitude and/or phase of the alternating current flowing through thewire 4604 as well as controlling switches 4640, 4642, 4644, and 4646 toregulate the magnetic flux of the magnetic core 4606 as previouslydescribed. If there is insufficient energy to perform these functions,the processing circuit can be configured to enter a sleep state wherethe processing circuit draws the least amount of power possible or toshut down entirely, while it awaits for the capacitor 4624 to achieve agreater charger via the configuration of diodes 4641 described earlier.

Once the processing circuit detects that there is a sufficient charge tocontrol switches 4640, 4642, 4644, and 4646, the processing circuit canproceed to step 4664 where it can be configured to perform a measurementof the alternating current flowing through the wire 4604 via, forexample, a resistive load coupled to the windings 4614. Step 4664 can beperformed by the processing circuit biasing the switches 4640, 4642,4644, and 4646 to short the windings 4614 for a given time interval suchas a half period of the operating frequency of the alternating currentflowing through the wire 4604. This can be accomplished by closingswitches 4640 (SW1) and 4644 (SW3), and opening switches 4642 (SW2) and4646 (SW4) (or, equivalently, by closing switches 4642 (SW2) and 4646(SW4), and opening switches 4640 (SW1) and 4644 (SW3)).

It is well known that an electronic switch such as MOSFET switch has anintrinsic resistance when it is biased in a closed position. Theintrinsic resistance can vary according to ambient temperature and agate-voltage bias applied to the switch. Assuming the switches 4640,4642, 4644, and 4646 illustrated in FIG. 46O have this intrinsicresistance (not shown), the processing circuit can be configured toperform a voltage measurement across one of the switches (e.g., switch4640 (SW1)) using a voltage sensor (e.g., an analog to digital converterand other circuitry), which can be integral to the processing circuit.The processing circuit can measure the voltage across the switch inreal-time and calculate from a sampling of voltage measurementscharacteristics of the alternating current such as its frequency, phaseand an amplitude of current flowing through the wire 4604.

To increase an accuracy of a phase and current amplitude calculation,the processing circuit can include a temperature sensor to measure atemperature in a vicinity of the switch being used for the measurement.Knowing the local temperature and a magnitude of a voltage bias appliedto the switch by the processing circuit, the processing circuit canobtain an estimate of the intrinsic resistance of the switch via alook-up table indexed by the local temperature and bias voltage. Theentry in the table can provide an estimate of the intrinsic resistanceof the switch while the measurement is being performed. The phase of thealternating current can be measured by detecting a zero crossing of thealternating current based on the voltage samples collected by theprocessing circuit. The frequency or, equivalently, the period of thealternating current can be measured by detecting a plurality of zerocrossings. Once determined, the processing circuit can be configured tosynchronize an internal clock utilizing a phase-locked loop circuit orother suitable synchronization technology based on the detected zerocrossings. Additionally, an amplitude of the current of the alternatingcurrent flowing through the wire 4604 can be calculated using Ohm's lawby measuring a peak voltage from the samples collected at step 4664 andusing the estimated intrinsic resistance of the switch to perform thecalculation. It will be appreciated that the phase, frequency andamplitude calculations can be performed according to multiple instancesof step 4664 which rely on averages of voltage samples collected.

Once the processing circuit has determined at step 4664 the phase of thealternating current thereby synchronizing its internal clock to thealternating current, it can proceed to step 4666 where it can generatean alternating voltage waveform 4630 by selectively connecting thestorage device 4624 to the windings 4614 of the magnetic core 4604. Inparticular, the processing circuit can be configured to generate thepositive part of the voltage waveform 4630 shown in FIG. 46L by closingswitches 4640 (SW1) and 4646 (SW4) and opening switches 4642 (SW2) and4644 (SW3). The negative part of the voltage waveform 4630 can beaccomplished by closing switches 4642 (SW2) and 4644 (SW3) and openingswitches 4640 (SW1) and 4646 (SW4). The part of the voltage waveform4630 where the voltage is zero is accomplished by closing switches 4640(SW1) and 4644 (SW3) and opening switches 4642 (SW2) and 4646 (SW4) (or,equivalently, by closing switches 4642 (SW2) and 4646 (SW4) and openingswitches 4640 (SW1) and 4644 (SW3)). Over time the voltage waveform 4630increases the magnetic flux flowing through the magnetic core 4606,which in turn increases a transfer of energy from the alternatingcurrent flowing through the wire 4604 to the windings 4614. This in turnincreases the charge of the capacitor 4624 to its fullest capacity. Thisprocess enables the processing circuit to regulate at step 4668 thealternating magnetic flux in the magnetic core 4606 via a selectivecontrol of the alternating voltage waveform 4630 applied to the windings4614.

In embodiments wherein the alternating current flowing through the wire4604 is periodic, the voltage waveform generated by waveform generator4626 is also periodic and synchronous with the periodic alternatingcurrent. In such embodiments, the duration of a period of the periodicvoltage waveform is the same as the duration of a period of the periodicalternating current. In other words, in such embodiments, the periodicvoltage waveform will vary, as a function of time, in accordance with aperiodic pattern of variations that repeats periodically in synchronywith the periodic variations of the alternating current flowing throughthe wire 4604. The magnetic flux also varies periodically, with the sameperiod duration, in accordance with a pattern of variations that isregulated by the periodic voltage waveform.

At step 4670, the processing circuit can be configured to, occasionally,(e.g., every few seconds, minutes, hours, days or combinations) toselect a part or more of a period of the alternating current (e.g., ahalf period, or greater or less, or even an entire period or more thanone period) to monitor characteristics of the alternating currentflowing through the wire 4604. For example, the processing circuit canproceed to step 4664 to measure once again characteristics of thealternating current (e.g., phase and/or current amplitude). During thistime, the capacitor 4624 may lose charge. To mitigate this loss, abackup battery (not shown) can be coupled to the capacitor 4624 toprovide a charge to the capacitor 4624 while it is disconnected from thewindings 4614. Coupling of the backup battery to the capacitor 4624 canbe selectively controlled by the processing circuit using additionalswitches not shown, or the backup battery can be coupled to thecapacitor 4642 by other means with circuitry that can enable charging ofthe capacitor 4624 while it is disconnected from the winding 4614.Alternatively, the capacitor can be made large enough to store enoughcharge for the duration of the selected part or more of a period. Theoccasional measurement of the phase of the alternating current canenable the processing circuit to more accurately synchronize the voltagewaveform 4630 to the magnetic flux caused by the alternating current sothat it can effectively regulate the magnetic flux in the magnetic core4606.

While performing the measurement of step 4664, the periodic variationsof magnetic flux resulting from the periodic voltage waveform can be animpediment to obtaining accurate results. In embodiments of the subjectdisclosure, the pattern of variations of the periodic voltage waveformcan be modified in a time interval during or around the time of ameasurement. The modified pattern of variations can be selected toachieve a modified pattern of magnetic flux variations that is bettersuited to achieving an accurate measurement. For example, the modifiedpattern might begin at a point, in the periodic variations of themagnetic flux, where the flux is near zero. At that point, the modifiedpattern might include a time interval of near-zero voltage, in order tomaintain the flux value near zero. Having near-zero magnetic flux duringa measurement can make it easier to predict the behavior of a magneticcore and how the magnetic core affects the measurement. In particular,the current flowing through a shorted winding is likely to be a moreaccurate representation of the alternating current, during such ameasurement.

It will be appreciated that method 4660 can be further adapted accordingto steps 4672 and 4674 as illustrated in FIG. 46P. During the executionof steps 4662 through 4670, the enhanced magnetic flux flowing throughthe magnetic core 4606 causes a coupling force between first and secondseparable portions 4613A and 4613B of the magnetic core 4606 to stronglyadhere to each other, which makes mechanical separation of the first andsecond separable portions 4613A and 4613B difficult to achieve while themagnetic flux is optimal. To enable de-installation or separation of thefirst and second separable portions 4613A and 4613B of the magnetic core4606, the processing system can be adapted to proceed from step 4670 tostep 4672 where a determination can be made by the processing systemwhether the first and second separable portions 4613A and 4613B need tobe decoupled. Step 4672 can be triggered upon receiving a wired signal,a wireless signal, a guided electromagnetic wave received from the wire4604, an electromechanical signal, or other forms of notification toinitiate a decoupling of the first and second separable portions 4613Aand 4613B of the magnetic core 4606.

The inductive power supply 4601 (and other devices, e.g., a waveguidesystem powered by the inductive power supply) can be placed in a housingassembly 4682 illustrated in FIGS. 46Q1 and 46Q2. The housing assembly4682 can be constructed of plastic or other materials sufficientlystrong to hold the inductive power supply 4601 (and other components).The first and second separable portions 4613A and 4613B of the magneticcore 4606 can be attached or placed along inner surfaces of first andsecond separable portions 4686A and 4686B, respectively, of the housingassembly 4682. The housing assembly 4682 can be adapted with one or morehinges (not shown) for opening and closing the first and secondseparable portions 4686A and 4686B of the housing assembly 4682. When inthe closed position, the first and second separable portions 4686A and4686B of the housing assembly 4682 meet at a borderline 4684 illustratedin FIGS. 46Q1 and 46Q2. The first and second separable portions 4686Aand 4686B of the housing assembly 4682 can be held in a closed positionwith a latch 4686. The latch 4686 can be pulled or otherwise disengagedto initiate a process for opening the housing assembly 4682.

In one embodiment, a mechanical release of the latch 4686 can beconfigured to generate an electromechanical signal detectable by theprocessing system (e.g., causing a detectable open or closed circuitwhen the latch is opened). In another embodiment, the mechanical releaseof the latch 4686 can cause an electromechanical switch to engage suchas SW5A 4647A or SW5B 4647B. In yet another embodiment, field personnel(or an unmanned aircraft) can place a magnet near the latch (or othersection of the housing assembly 4682) to engage a switch (e.g., SW5A4647A or SW5B 4647B) as a result of the magnetic field (e.g., a Reedswitch). In another embodiment, a wireless signal can be generated,which can be detectable by the processing system via a receiverconfigured with an antenna that can receive and process the wirelesssignal. The wireless signal can convey a de-installation message orsignal. In another embodiment, a cable (not shown) can be tethered tothe processing system via a port of the housing assembly 4682 (notshown) enabling supply of a wired signal to the processing system. Thewired signal can convey a de-installation message or signal. In yetanother embodiment, a waveguide receiver powered by the inductive powersupply 4606 can be configured to receive an electromagnetic wavepropagating along the wire 4604. The electromagnetic wave can convey ade-installation message or signal.

In one embodiment, when a de-installation signal conveyed by anelectromechanical effect (e.g., due to disengaging the latch 4686) or amagnetic field effect (e.g., due to placement of a magnet near one ofthese switches) is detected at step 4672, switch SW5A 4647A or switchSW5B 4647B can be engaged without the use of the processing system totrigger the engagement of either of these switches. Engaging switch SW5A4647A or switch SW5B 4647B causes an electrical short across winding4614 or an electrical short across storage device 4624, which in turnsignificantly reduces the magnetic flux flowing through the magneticcore 4606. A reduced magnetic flux in turn substantially decreases thecoupling force between the first and second separable portions 4613A and4613B of the magnetic core 4606 so as to decrease their adherence toeach other, thereby enabling physical decoupling at step 4674 of thefirst and second separable portions 4613A and 4613B of the magnetic core4606.

In another embodiment, when a de-installation message or signal conveyedby a wireless signal, wired signal, or received electromagnetic wave isdetected at step 4672 by the processing system, the processing systemcan proceed to step 4674 where it configures one or more switches. Forexample, in one embodiment, the processing system can engage switchesSW2 4642 and SW4 4646, while maintaining switches SW1 4640 and SW3 4644disengaged. In this embodiment, the winding 4614 is electrically shorted(without shorting the storage device 4624), which reduces the magneticflux in the magnetic core 4606, thereby enabling decoupling of the firstand second separable portions 4613A and 4613B of the magnetic core 4606at step 4674. In another embodiment, the processing system can engageswitches SW1 4640 and SW3 4644, while maintaining switches SW2 4642 andSW4 4646 disengaged. In this embodiment, the winding 4614 iselectrically shorted (without shorting the storage device 4624), whichreduces the magnetic flux in the magnetic core 4606, thereby enablingdecoupling of the first and second separable portions 4613A and 4613B ofthe magnetic core 4606 at step 4674. In yet another embodiment, theprocessing system can engage all switches (i.e., SW1 4640, SW2 4642, SW34644 and SW4 4646). In this embodiment, the winding 4614 is electricallyshorted and the storage device 4624 is shorted, either one reducing themagnetic flux in the magnetic core 4606, which enables decoupling of thefirst and second separable portions 4613A and 4613B of the magnetic core4606 at step 4674. In yet another embodiment, the processing system canengage switch SW5A 4647A or switch SW5B 4647B, which shorts winding 4614or storage device 4624, either one reducing the magnetic flux in themagnetic core 4606, which enables decoupling of the first and secondseparable portions 4613A and 4613B of the magnetic core 4606 at step4674.

In yet another embodiment, the processing system can be configured todynamically configure switches SW1 4640 through SW4 4646 to cause areverse configuration of the alternating voltage waveform 4630 (see FIG.46L) so as to cause a magnetic flux that is opposite in phase to themagnetic flux caused by the alternating current flowing through the wire4604. The result of this reversal is to reduce, if not substantiallyeliminate, the magnetic flux flowing in the magnetic core 4606, whichenables decoupling of the first and second separable portions 4613A and4613B of the magnetic core 4606 at step 4674.

It will be appreciated that any technique that reduces the magnetic fluxflowing through the magnetic core 4606 can be used to enable decouplingof the first and second separable portions 4613A and 4613B of themagnetic core 4606 at step 4674. It will be further appreciated that theprocessing system can be configured to utilize the remaining energy inthe storage device 4624 (when not shorted) to power itself and othercomponents, or utilize another storage device (e.g., backup battery) notshown to do the same. This can be helpful during maintenance operations.For example, when the housing assembly 4682 is opened for maintenancepurposes, the processing system can enter a sleep state or low powermonitoring state of step 4672 after enabling decoupling of the first andsecond separable portions 4613A and 4613B of the magnetic core 4606 atstep 4674. When the processing system detects that the housing assembly4682 has been closed via an electromechanical or magnetic signal, theprocessing system can proceed to step 4664 to initiate the waveformgeneration process previously described.

Alternatively, when the processing system detects a wireless signal,wired signal, or electromagnetic wave that conveys a message or signalindicating the housing assembly 4682 has been closed and/or theinductive supply is to be turned on signal, then the processing systemcan proceed to step 4664 to initiate the waveform generation processpreviously described. If, on the other hand, there is no energy in thestorage device 4624 as a result of it being shorted or depleted inenergy due to a long period of non-use, and/or the processing systemdoes not have a backup supply or other source of energy, then theprocessing system can be re-energized via the power-on sequence of step4662, and once powered, reinitiate the waveform generation processbeginning at step 4664.

It will be clear to those skilled in the art, after reading the subjectdisclosure, that a near-zero magnetic flux means a magnetic fluxsufficiently small to make the effect of the magnetic flux negligible;i.e., the disruption caused by such magnetic flux, when compared toother sources of error, relative to a desired level of accuracy, can besafely neglected. Alternatively, the modified pattern of variations ofthe periodic voltage waveform can be selected to achieve a modifiedpattern of magnetic-flux variations which, though non-negligible, hasdesirable characteristics for performing measurements.

The amplitude of the current measured by the processing circuit can bestored or reported. For example, the alternating current flowing throughthe wire 4604 may be sourced by a power utility company. The amplitudeof current measured by the processing circuit can be reported to a powerutility company for monitoring purposes. Such information can enable thepower utility to profile power usage at different times of the day. Awaveguide system utilizing the inductive power supply described abovecan be configured to transmit electromagnetic waves that includemeasurement information associated with the signal. The electromagneticwaves can propagate over power lines to a network of other waveguidesystems, which can convey such measurements to the utility company at aparticular network element. It will be appreciated that other telemetrydata can be conveyed to the utility company such as local temperature,measured phase of the power signal, and other information that may beuseful to the utility company.

While for purposes of simplicity of explanation, the respectiveprocesses are shown and described as a series of blocks in FIGS. 46N and46P, it is to be understood and appreciated that the claimed subjectmatter is not limited by the order of the blocks, as some blocks mayoccur in different orders and/or concurrently with other blocks fromwhat is depicted and described herein. Moreover, not all illustratedblocks may be required to implement the methods described herein.

It is further appreciated that the foregoing embodiments associated withFIGS. 46K-46P can be combined in whole or in part with one another,and/or can be combined in whole or in part with other embodiments of thesubject disclosure, and/or can be adapted for use in whole or in partwith other embodiments of the subject disclosure.

It is further appreciated that any of the embodiments of the subjectdisclosure (singly or in any combination) which are adaptable fortransmitting or receiving communication signals can be utilized asnetwork elements for the distribution and/or routing of media content,voice communications, video streaming, internet traffic or other datatransport. It is further appreciated that such network elements can beadapted or otherwise utilized in a communication network described belowin relation to FIG. 47 for the distribution or routing of media content,voice communications, video streaming, internet traffic or other datatransport. It is also appreciated that such network elements can also beconfigured to utilize virtualized communication network techniquesdescribed below in relation to FIG. 48.

Referring now to FIG. 47, a block diagram is shown illustrating anexample, non-limiting embodiment of a communications network 4700 inaccordance with various aspects described herein. In particular, acommunications network 4725 is presented for providing broadband access4710 to a plurality of data terminals 4714 via access terminal 4712,wireless access 4720 to a plurality of mobile devices 4724 and vehicle4726 via base station or access point 4722, voice access 4730 to aplurality of telephony devices 4734, via switching device 4732 and/ormedia access 4740 to a plurality of audio/video display devices 4744 viamedia terminal 4742. In addition, communication network 4725 is coupledto one or more content sources 4775 of audio, video, graphics, textand/or other media. While broadband access 4710, wireless access 4720,voice access 4730 and media access 4740 are shown separately, one ormore of these forms of access can be combined to provide multiple accessservices to a single client device (e.g., mobile devices 4724 canreceive media content via media terminal 4742, data terminal 4714 can beprovided voice access via switching device 4732, and so on).

The communications network 4725 includes a plurality of network elements(NE) 4750, 4752, 4754, 4756, etc. for facilitating the broadband access4710, wireless access 4720, voice access 4730, media access 4740 and/orthe distribution of content from content sources 4775. Thecommunications network 4725 can include a circuit switched or packetswitched network, a voice over Internet protocol (VoIP) network,Internet protocol (IP) network, a cable network, a passive or activeoptical network, a 4G, 5G, or higher generation wireless access network,WIMAX network, UltraWideband network, personal area network or otherwireless access network, a broadcast satellite network and/or othercommunications network.

In various embodiments, the access terminal 4712 can include a digitalsubscriber line access multiplexer (DSLAM), cable modem terminationsystem (CMTS), optical line terminal (OLT) and/or other access terminal.The data terminals 4714 can include personal computers, laptopcomputers, netbook computers, tablets or other computing devices alongwith digital subscriber line (DSL) modems, data over coax serviceinterface specification (DOCSIS) modems or other cable modems, awireless modem such as a 4G, 5G, or higher generation modem, an opticalmodem and/or other access devices.

In various embodiments, the base station or access point 4722 caninclude a 4G, 5G, or higher generation base station, an access pointthat operates via an 802.11 standard such as 802.11n, 802.11ac,802.11ag, 802.11agn or other wireless access terminal. The mobiledevices 4724 can include mobile phones, e-readers, tablets, phablets,wireless modems, and/or other mobile computing devices.

In various embodiments, the switching device 4732 can include a privatebranch exchange or central office switch, a media services gateway, VoIPgateway or other gateway device and/or other switching device. Thetelephony devices 4734 can include traditional telephones (with orwithout a terminal adapter), VoIP telephones and/or other telephonydevices.

In various embodiments, the media terminal 4742 can include a cablehead-end or other TV head-end, a satellite receiver, gateway or othermedia terminal 4742. The display devices 4744 can include televisionswith or without a set top box, personal computers and/or other displaydevices.

In various embodiments, the content sources 4775 include broadcasttelevision and radio sources, video on demand platforms and streamingvideo and audio services platforms, one or more content data networks,data servers, web servers and other content servers, and/or othersources of media.

In various embodiments, the communications network 4725 can includewired, optical and/or wireless links and the network elements 4750,4752, 4754, 4756, etc. can include service switching points, signaltransfer points, service control points, network gateways, mediadistribution hubs, servers, firewalls, routers, edge devices, switchesand other network nodes for routing and controlling communicationstraffic over wired, optical and wireless links as part of the Internetand other public networks as well as one or more private networks, formanaging subscriber access, for billing and network management and forsupporting other network functions.

It will be appreciated that any of the subsystems (e.g., access terminal4712, network elements 4750-4756, media terminal 4742, switching device4732, wireless access 4720, and so on) of the communication network 4700can be configured or otherwise adapted to utilize in whole or in partany of the embodiments of the subject disclosure for transmitting andreceiving communication signals via electromagnetic waves that propagateover wireless or physical transmission media.

Referring now to FIG. 48, a block diagram 4800 is shown illustrating anexample, non-limiting embodiment of a virtualized communication networkin accordance with various aspects described herein. In particular avirtualized communication network is presented that can be used toimplement some or all of the subsystems and functions of communicationnetwork 4700, some or all of the embodiments associated with waveguidesystems and methods thereof, some or all of the embodiments associatedwith distributed antenna systems, or other embodiments and methodsthereof described by the subject disclosure.

In particular, a cloud networking architecture is shown that leveragescloud technologies and supports rapid innovation and scalability via atransport layer 4850, a virtualized network function cloud 4825 and/orone or more cloud computing environments 4875. In various embodiments,this cloud networking architecture is an open architecture thatleverages application programming interfaces (APIs); reduces complexityfrom services and operations; supports more nimble business models; andrapidly and seamlessly scales to meet evolving customer requirementsincluding traffic growth, diversity of traffic types, and diversity ofperformance and reliability expectations.

In contrast to traditional network elements—which are typicallyintegrated to perform a single function, the virtualized communicationnetwork employs virtual network elements 4830, 4832, 4834, etc. thatperform some or all of the functions of network elements 150, 152, 154,156, etc. For example, the network architecture can provide a substrateof networking capability, often called Network Function VirtualizationInfrastructure (NFVI) or simply infrastructure that is capable of beingdirected with software and Software Defined Networking (SDN) protocolsto perform a broad variety of network functions and services. Thisinfrastructure can include several types of substrates. The most typicaltype of substrate being servers that support Network FunctionVirtualization (NFV), followed by packet forwarding capabilities basedon generic computing resources, with specialized network technologiesbrought to bear when general purpose processors or general purposeintegrated circuit devices offered by merchants (referred to herein asmerchant silicon) are not appropriate. In this case, communicationservices can be implemented as cloud-centric workloads.

As an example, a traditional network element 150 (shown in FIG. 1), suchas an edge router can be implemented via a virtual network element 4830composed of NFV software modules, merchant silicon, and associatedcontrollers. The software can be written so that increasing workloadconsumes incremental resources from a common resource pool, and moreoverso that it's elastic: so the resources are only consumed when needed. Ina similar fashion, other network elements such as other routers,switches, edge caches, and middle-boxes are instantiated from the commonresource pool. Such sharing of infrastructure across a broad set of usesmakes planning and growing infrastructure easier to manage.

In an embodiment, the transport layer 4850 includes fiber, cable, wiredand/or wireless transport elements, network elements and interfaces toprovide broadband access 4710, wireless access 4720, voice access 4730,media access 4740 and/or access to content sources 4775 for distributionof content to any or all of the access technologies. In particular, insome cases a network element needs to be positioned at a specific place,and this allows for less sharing of common infrastructure. Other times,the network elements have specific physical layer adapters that cannotbe abstracted or virtualized, and might require special DSP code andanalog front-ends (AFEs) that do not lend themselves to implementationas virtual network elements 4830, 4832 or 4834. These network elementscan be included in transport layer 4850.

The virtualized network function cloud 4825 interfaces with thetransport layer 4850 to provide the virtual network elements 4830, 4832,4834, etc. to provide specific NFVs. In particular, the virtualizednetwork function cloud 4825 leverages cloud operations, applications,and architectures to support networking workloads. The virtualizednetwork elements 4830, 4832 and 4834 can employ network functionsoftware that provides either a one-for-one mapping of traditionalnetwork element function or alternately some combination of networkfunctions designed for cloud computing. For example, virtualized networkelements 4830, 4832 and 4834 can include route reflectors, domain namesystem (DNS) servers, and dynamic host configuration protocol (DHCP)servers, system architecture evolution (SAE) and/or mobility managemententity (MME) gateways, broadband network gateways, IP edge routers forIP-VPN, Ethernet and other services, load balancers, distributers andother network elements. Because these elements don't typically need toforward large amounts of traffic, their workload can be distributedacross a number of servers—each of which adds a portion of thecapability, and overall which creates an elastic function with higheravailability than its former monolithic version. These virtual networkelements 4830, 4832, 4834, etc. can be instantiated and managed using anorchestration approach similar to those used in cloud compute services.

The cloud computing environments 4875 can interface with the virtualizednetwork function cloud 4825 via APIs that expose functional capabilitiesof the VNE 4830, 4832, 4834, etc. to provide the flexible and expandedcapabilities to the virtualized network function cloud 4825. Inparticular, network workloads may have applications distributed acrossthe virtualized network function cloud 4825 and cloud computingenvironment 4875 and in the commercial cloud, or might simplyorchestrate workloads supported entirely in NFV infrastructure fromthese third party locations.

It will be appreciated that any of the foregoing techniques can beapplied or combined in whole or in party with any embodiments of thesubsystems and functions of communication network 4700, some or all ofthe embodiments associated with waveguide systems and methods thereof,some or all of the embodiments associated with distributed antennasystems, as well as other embodiments and methods thereof described bythe subject disclosure.

Referring now to FIG. 49, there is illustrated a block diagram of acomputing environment in accordance with various aspects describedherein. In order to provide additional context for various embodimentsof the embodiments described herein, FIG. 49 and the followingdiscussion are intended to provide a brief, general description of asuitable computing environment 4900 in which the various embodiments ofthe subject disclosure can be implemented. While the embodiments havebeen described above in the general context of computer-executableinstructions that can run on one or more computers, those skilled in theart will recognize that the embodiments can be also implemented incombination with other program modules and/or as a combination ofhardware and software.

Generally, program modules comprise routines, programs, components, datastructures, etc., that perform particular tasks or implement particularabstract data types. Moreover, those skilled in the art will appreciatethat the inventive methods can be practiced with other computer systemconfigurations, comprising single-processor or multiprocessor computersystems, minicomputers, mainframe computers, as well as personalcomputers, hand-held computing devices, microprocessor-based orprogrammable consumer electronics, and the like, each of which can beoperatively coupled to one or more associated devices.

As used herein, a processing circuit includes processor as well as otherapplication specific circuits such as an application specific integratedcircuit, digital logic circuit, state machine, programmable gate arrayor other circuit that processes input signals or data and that producesoutput signals or data in response thereto. It should be noted thatwhile any functions and features described herein in association withthe operation of a processor could likewise be performed by a processingcircuit.

The terms “first,” “second,” “third,” and so forth, as used in theclaims, unless otherwise clear by context, is for clarity only anddoesn't otherwise indicate or imply any order in time. For instance, “afirst determination,” “a second determination,” and “a thirddetermination,” does not indicate or imply that the first determinationis to be made before the second determination, or vice versa, etc.

The illustrated embodiments of the embodiments herein can be alsopracticed in distributed computing environments where certain tasks areperformed by remote processing devices that are linked through acommunications network. In a distributed computing environment, programmodules can be located in both local and remote memory storage devices.

Computing devices typically comprise a variety of media, which cancomprise computer-readable storage media and/or communications media,which two terms are used herein differently from one another as follows.Computer-readable storage media can be any available storage media thatcan be accessed by the computer and comprises both volatile andnonvolatile media, removable and non-removable media. By way of example,and not limitation, computer-readable storage media can be implementedin connection with any method or technology for storage of informationsuch as computer-readable instructions, program modules, structured dataor unstructured data.

Computer-readable storage media can comprise, but are not limited to,random access memory (RAM), read only memory (ROM), electricallyerasable programmable read only memory (EEPROM), flash memory or othermemory technology, compact disk read only memory (CD-ROM), digitalversatile disk (DVD) or other optical disk storage, magnetic cassettes,magnetic tape, magnetic disk storage or other magnetic storage devicesor other tangible and/or non-transitory media which can be used to storedesired information. In this regard, the terms “tangible” or“non-transitory” herein as applied to storage, memory orcomputer-readable media, are to be understood to exclude onlypropagating transitory signals per se as modifiers and do not relinquishrights to all standard storage, memory or computer-readable media thatare not only propagating transitory signals per se.

Computer-readable storage media can be accessed by one or more local orremote computing devices, e.g., via access requests, queries or otherdata retrieval protocols, for a variety of operations with respect tothe information stored by the medium.

Communications media typically embody computer-readable instructions,data structures, program modules or other structured or unstructureddata in a data signal such as a modulated data signal, e.g., a carrierwave or other transport mechanism, and comprises any informationdelivery or transport media. The term “modulated data signal” or signalsrefers to a signal that has one or more of its characteristics set orchanged in such a manner as to encode information in one or moresignals. By way of example, and not limitation, communication mediacomprise wired media, such as a wired network or direct-wiredconnection, and wireless media such as acoustic, RF, infrared and otherwireless media.

With reference again to FIG. 49, the example environment 4900 fortransmitting and receiving signals via or forming at least part of abase station (e.g., base station devices 1504, macrocell site 1502, orbase stations 1614) or central office (e.g., central office 1501 or1611). At least a portion of the example environment 4900 can also beused for transmission devices 101 or 102. The example environment cancomprise a computer 4902, the computer 4902 comprising a processing unit4904, a system memory 4906 and a system bus 4908. The system bus 4908couple's system components including, but not limited to, the systemmemory 4906 to the processing unit 4904. The processing unit 4904 can beany of various commercially available processors. Dual microprocessorsand other multiprocessor architectures can also be employed as theprocessing unit 4904.

The system bus 4908 can be any of several types of bus structure thatcan further interconnect to a memory bus (with or without a memorycontroller), a peripheral bus, and a local bus using any of a variety ofcommercially available bus architectures. The system memory 4906comprises ROM 4910 and RAM 4912. A basic input/output system (BIOS) canbe stored in a non-volatile memory such as ROM, erasable programmableread only memory (EPROM), EEPROM, which BIOS contains the basic routinesthat help to transfer information between elements within the computer4902, such as during startup. The RAM 4912 can also comprise ahigh-speed RAM such as static RAM for caching data.

The computer 4902 further comprises an internal hard disk drive (HDD)4914 (e.g., EIDE, SATA), which internal hard disk drive 4914 can also beconfigured for external use in a suitable chassis (not shown), amagnetic floppy disk drive (FDD) 4916, (e.g., to read from or write to aremovable diskette 4918) and an optical disk drive 4920, (e.g., readinga CD-ROM disk 4922 or, to read from or write to other high capacityoptical media such as the DVD). The hard disk drive 4914, magnetic diskdrive 4916 and optical disk drive 4920 can be connected to the systembus 4908 by a hard disk drive interface 4924, a magnetic disk driveinterface 4926 and an optical drive interface 4928, respectively. Theinterface 4924 for external drive implementations comprises at least oneor both of Universal Serial Bus (USB) and Institute of Electrical andElectronics Engineers (IEEE) 1394 interface technologies. Other externaldrive connection technologies are within contemplation of theembodiments described herein.

The drives and their associated computer-readable storage media providenonvolatile storage of data, data structures, computer-executableinstructions, and so forth. For the computer 4902, the drives andstorage media accommodate the storage of any data in a suitable digitalformat. Although the description of computer-readable storage mediaabove refers to a hard disk drive (HDD), a removable magnetic diskette,and a removable optical media such as a CD or DVD, it should beappreciated by those skilled in the art that other types of storagemedia which are readable by a computer, such as zip drives, magneticcassettes, flash memory cards, cartridges, and the like, can also beused in the example operating environment, and further, that any suchstorage media can contain computer-executable instructions forperforming the methods described herein.

A number of program modules can be stored in the drives and RAM 4912,comprising an operating system 4930, one or more application programs4932, other program modules 4934 and program data 4936. All or portionsof the operating system, applications, modules, and/or data can also becached in the RAM 4912. The systems and methods described herein can beimplemented utilizing various commercially available operating systemsor combinations of operating systems. Examples of application programs4932 that can be implemented and otherwise executed by processing unit4904 include the diversity selection determining performed bytransmission device 101 or 102.

A user can enter commands and information into the computer 4902 throughone or more wired/wireless input devices, e.g., a keyboard 4938 and apointing device, such as a mouse 4940. Other input devices (not shown)can comprise a microphone, an infrared (IR) remote control, a joystick,a game pad, a stylus pen, touch screen or the like. These and otherinput devices are often connected to the processing unit 4904 through aninput device interface 4942 that can be coupled to the system bus 4908,but can be connected by other interfaces, such as a parallel port, anIEEE 1394 serial port, a game port, a universal serial bus (USB) port,an IR interface, etc.

A monitor 4944 or other type of display device can be also connected tothe system bus 4908 via an interface, such as a video adapter 4946. Itwill also be appreciated that in alternative embodiments, a monitor 4944can also be any display device (e.g., another computer having a display,a smart phone, a tablet computer, etc.) for receiving displayinformation associated with computer 4902 via any communication means,including via the Internet and cloud-based networks. In addition to themonitor 4944, a computer typically comprises other peripheral outputdevices (not shown), such as speakers, printers, etc.

The computer 4902 can operate in a networked environment using logicalconnections via wired and/or wireless communications to one or moreremote computers, such as a remote computer(s) 4948. The remotecomputer(s) 4948 can be a workstation, a server computer, a router, apersonal computer, portable computer, microprocessor-based entertainmentappliance, a peer device or other common network node, and typicallycomprises many or all of the elements described relative to the computer4902, although, for purposes of brevity, only a memory/storage device4950 is illustrated. The logical connections depicted comprisewired/wireless connectivity to a local area network (LAN) 4952 and/orlarger networks, e.g., a wide area network (WAN) 4954. Such LAN and WANnetworking environments are commonplace in offices and companies, andfacilitate enterprise-wide computer networks, such as intranets, all ofwhich can connect to a global communications network, e.g., theInternet.

When used in a LAN networking environment, the computer 4902 can beconnected to the local network 4952 through a wired and/or wirelesscommunication network interface or adapter 4956. The adapter 4956 canfacilitate wired or wireless communication to the LAN 4952, which canalso comprise a wireless AP disposed thereon for communicating with thewireless adapter 4956.

When used in a WAN networking environment, the computer 4902 cancomprise a modem 4958 or can be connected to a communications server onthe WAN 4954 or has other means for establishing communications over theWAN 4954, such as by way of the Internet. The modem 4958, which can beinternal or external and a wired or wireless device, can be connected tothe system bus 4908 via the input device interface 4942. In a networkedenvironment, program modules depicted relative to the computer 4902 orportions thereof, can be stored in the remote memory/storage device4950. It will be appreciated that the network connections shown areexample and other means of establishing a communications link betweenthe computers can be used.

The computer 4902 can be operable to communicate with any wirelessdevices or entities operatively disposed in wireless communication,e.g., a printer, scanner, desktop and/or portable computer, portabledata assistant, communications satellite, any piece of equipment orlocation associated with a wirelessly detectable tag (e.g., a kiosk,news stand, restroom), and telephone. This can comprise WirelessFidelity (Wi-Fi) and Bluetooth® wireless technologies. Thus, thecommunication can be a predefined structure as with a conventionalnetwork or simply an ad hoc communication between at least two devices.

Wi-Fi can allow connection to the Internet from a couch at home, a bedin a hotel room or a conference room at work, without wires. Wi-Fi is awireless technology similar to that used in a cell phone that enablessuch devices, e.g., computers, to send and receive data indoors and out;anywhere within the range of a base station. Wi-Fi networks use radiotechnologies called IEEE 802.11 (a, b, g, n, ac, ag etc.) to providesecure, reliable, fast wireless connectivity. A Wi-Fi network can beused to connect computers to each other, to the Internet, and to wirednetworks (which can use IEEE 802.3 or Ethernet). Wi-Fi networks operatein the unlicensed 2.4 and 5 GHz radio bands for example or with productsthat contain both bands (dual band), so the networks can providereal-world performance similar to the basic 10BaseT wired Ethernetnetworks used in many offices.

FIG. 50 presents an example embodiment 5000 of a mobile network platform5010 that can implement and exploit one or more aspects of the disclosedsubject matter described herein. In one or more embodiments, the mobilenetwork platform 5010 can generate and receive signals transmitted andreceived by base stations (e.g., base station devices 1504, macrocellsite 1502, or base stations 1614), central office (e.g., central office1501 or 1611), or transmission device 101 or 102 associated with thedisclosed subject matter. Generally, wireless network platform 5010 cancomprise components, e.g., nodes, gateways, interfaces, servers, ordisparate platforms, that facilitate both packet-switched (PS) (e.g.,internet protocol (IP), frame relay, asynchronous transfer mode (ATM))and circuit-switched (CS) traffic (e.g., voice and data), as well ascontrol generation for networked wireless telecommunication. As anon-limiting example, wireless network platform 5010 can be included intelecommunications carrier networks, and can be considered carrier-sidecomponents as discussed elsewhere herein. Mobile network platform 5010comprises CS gateway node(s) 5022 which can interface CS trafficreceived from legacy networks like telephony network(s) 5040 (e.g.,public switched telephone network (PSTN), or public land mobile network(PLMN)) or a signaling system #7 (SS7) network 5070. Circuit switchedgateway node(s) 5022 can authorize and authenticate traffic (e.g.,voice) arising from such networks. Additionally, CS gateway node(s) 5022can access mobility, or roaming, data generated through SS7 network5070; for instance, mobility data stored in a visited location register(VLR), which can reside in memory 5030. Moreover, CS gateway node(s)5022 interfaces CS-based traffic and signaling and PS gateway node(s)5018. As an example, in a 3GPP UMTS network, CS gateway node(s) 5022 canbe realized at least in part in gateway GPRS support node(s) (GGSN). Itshould be appreciated that functionality and specific operation of CSgateway node(s) 5022, PS gateway node(s) 5018, and serving node(s) 5016,is provided and dictated by radio technology(ies) utilized by mobilenetwork platform 5010 for telecommunication.

In addition to receiving and processing CS-switched traffic andsignaling, PS gateway node(s) 5018 can authorize and authenticatePS-based data sessions with served mobile devices. Data sessions cancomprise traffic, or content(s), exchanged with networks external to thewireless network platform 5010, like wide area network(s) (WANs) 5050,enterprise network(s) 5070, and service network(s) 5080, which can beembodied in local area network(s) (LANs), can also be interfaced withmobile network platform 5010 through PS gateway node(s) 5018. It is tobe noted that WANs 5050 and enterprise network(s) 5060 can embody, atleast in part, a service network(s) like IP multimedia subsystem (IMS).Based on radio technology layer(s) available in technology resource(s)5017, packet-switched gateway node(s) 5018 can generate packet dataprotocol contexts when a data session is established; other datastructures that facilitate routing of packetized data also can begenerated. To that end, in an aspect, PS gateway node(s) 5018 cancomprise a tunnel interface (e.g., tunnel termination gateway (TTG) in3GPP UMTS network(s) (not shown)) which can facilitate packetizedcommunication with disparate wireless network(s), such as Wi-Finetworks.

In embodiment 5000, wireless network platform 5010 also comprisesserving node(s) 5016 that, based upon available radio technologylayer(s) within technology resource(s) 5017, convey the variouspacketized flows of data streams received through PS gateway node(s)5018. It is to be noted that for technology resource(s) 5017 that relyprimarily on CS communication, server node(s) can deliver trafficwithout reliance on PS gateway node(s) 5018; for example, server node(s)can embody at least in part a mobile switching center. As an example, ina 3GPP UMTS network, serving node(s) 5016 can be embodied in servingGPRS support node(s) (SGSN).

For radio technologies that exploit packetized communication, server(s)5014 in wireless network platform 5010 can execute numerous applicationsthat can generate multiple disparate packetized data streams or flows,and manage (e.g., schedule, queue, format . . . ) such flows. Suchapplication(s) can comprise add-on features to standard services (forexample, provisioning, billing, customer support . . . ) provided bywireless network platform 5010. Data streams (e.g., content(s) that arepart of a voice call or data session) can be conveyed to PS gatewaynode(s) 5018 for authorization/authentication and initiation of a datasession, and to serving node(s) 5016 for communication thereafter. Inaddition to application server, server(s) 5014 can comprise utilityserver(s), a utility server can comprise a provisioning server, anoperations and maintenance server, a security server that can implementat least in part a certificate authority and firewalls as well as othersecurity mechanisms, and the like. In an aspect, security server(s)secure communication served through wireless network platform 5010 toensure network's operation and data integrity in addition toauthorization and authentication procedures that CS gateway node(s) 5022and PS gateway node(s) 5018 can enact. Moreover, provisioning server(s)can provision services from external network(s) like networks operatedby a disparate service provider; for instance, WAN 5050 or GlobalPositioning System (GPS) network(s) (not shown). Provisioning server(s)can also provision coverage through networks associated to wirelessnetwork platform 5010 (e.g., deployed and operated by the same serviceprovider), such as the distributed antennas networks shown in FIG. 1that enhance wireless service coverage by providing more networkcoverage. Repeater devices such as those shown in FIGS. 7, 8, and 9 alsoimprove network coverage in order to enhance subscriber serviceexperience by way of UE 5075.

It is to be noted that server(s) 5014 can comprise one or moreprocessors configured to confer at least in part the functionality ofmacro network platform 5010. To that end, the one or more processor canexecute code instructions stored in memory 5030, for example. It isshould be appreciated that server(s) 5014 can comprise a content manager5015, which operates in substantially the same manner as describedhereinbefore.

In example embodiment 5000, memory 5030 can store information related tooperation of wireless network platform 5010. Other operationalinformation can comprise provisioning information of mobile devicesserved through wireless platform network 5010, subscriber databases;application intelligence, pricing schemes, e.g., promotional rates,flat-rate programs, couponing campaigns; technical specification(s)consistent with telecommunication protocols for operation of disparateradio, or wireless, technology layers; and so forth. Memory 5030 canalso store information from at least one of telephony network(s) 5040,WAN 5050, enterprise network(s) 5070, or SS7 network 5060. In an aspect,memory 5030 can be, for example, accessed as part of a data storecomponent or as a remotely connected memory store.

In order to provide a context for the various aspects of the disclosedsubject matter, FIG. 50, and the following discussion, are intended toprovide a brief, general description of a suitable environment in whichthe various aspects of the disclosed subject matter can be implemented.While the subject matter has been described above in the general contextof computer-executable instructions of a computer program that runs on acomputer and/or computers, those skilled in the art will recognize thatthe disclosed subject matter also can be implemented in combination withother program modules. Generally, program modules comprise routines,programs, components, data structures, etc. that perform particulartasks and/or implement particular abstract data types.

FIG. 51 depicts an illustrative embodiment of a communication device5100. The communication device 5100 can serve as an illustrativeembodiment of devices such as mobile devices and in-building devicesreferred to by the subject disclosure (e.g., in FIGS. 15, 16A and 16B).

The communication device 5100 can comprise a wireline and/or wirelesstransceiver 5102 (herein transceiver 5102), a user interface (UI) 5104,a power supply 5114, a location receiver 5116, a motion sensor 5118, anorientation sensor 5120, and a controller 5106 for managing operationsthereof. The transceiver 5102 can support short-range or long-rangewireless access technologies such as Bluetooth®, ZigBee®, WiFi, DECT, orcellular communication technologies, just to mention a few (Bluetooth®and ZigBee® are trademarks registered by the Bluetooth® Special InterestGroup and the ZigBee® Alliance, respectively). Cellular technologies caninclude, for example, CDMA-1X, UMTS/HSDPA, GSM/GPRS, TDMA/EDGE, EV/DO,WiMAX, SDR, LTE, as well as other next generation wireless communicationtechnologies as they arise. The transceiver 5102 can also be adapted tosupport circuit-switched wireline access technologies (such as PSTN),packet-switched wireline access technologies (such as TCP/IP, VoIP,etc.), and combinations thereof.

The UI 5104 can include a depressible or touch-sensitive keypad 5108with a navigation mechanism such as a roller ball, a joystick, a mouse,or a navigation disk for manipulating operations of the communicationdevice 5100. The keypad 5108 can be an integral part of a housingassembly of the communication device 5100 or an independent deviceoperably coupled thereto by a tethered wireline interface (such as a USBcable) or a wireless interface supporting for example Bluetooth®. Thekeypad 5108 can represent a numeric keypad commonly used by phones,and/or a QWERTY keypad with alphanumeric keys. The UI 5104 can furtherinclude a display 5110 such as monochrome or color LCD (Liquid CrystalDisplay), OLED (Organic Light Emitting Diode) or other suitable displaytechnology for conveying images to an end user of the communicationdevice 5100. In an embodiment where the display 5110 is touch-sensitive,a portion or all of the keypad 5108 can be presented by way of thedisplay 5110 with navigation features.

The display 5110 can use touch screen technology to also serve as a userinterface for detecting user input. As a touch screen display, thecommunication device 5100 can be adapted to present a user interfacehaving graphical user interface (GUI) elements that can be selected by auser with a touch of a finger. The touch screen display 5110 can beequipped with capacitive, resistive or other forms of sensing technologyto detect how much surface area of a user's finger has been placed on aportion of the touch screen display. This sensing information can beused to control the manipulation of the GUI elements or other functionsof the user interface. The display 5110 can be an integral part of thehousing assembly of the communication device 5100 or an independentdevice communicatively coupled thereto by a tethered wireline interface(such as a cable) or a wireless interface.

The UI 5104 can also include an audio system 5112 that utilizes audiotechnology for conveying low volume audio (such as audio heard inproximity of a human ear) and high volume audio (such as speakerphonefor hands free operation). The audio system 5112 can further include amicrophone for receiving audible signals of an end user. The audiosystem 5112 can also be used for voice recognition applications. The UI5104 can further include an image sensor 5113 such as a charged coupleddevice (CCD) camera for capturing still or moving images.

The power supply 5114 can utilize common power management technologiessuch as replaceable and rechargeable batteries, supply regulationtechnologies, and/or charging system technologies for supplying energyto the components of the communication device 5100 to facilitatelong-range or short-range portable communications. Alternatively, or incombination, the charging system can utilize external power sources suchas DC power supplied over a physical interface such as a USB port orother suitable tethering technologies.

The location receiver 5116 can utilize location technology such as aglobal positioning system (GPS) receiver capable of assisted GPS foridentifying a location of the communication device 5100 based on signalsgenerated by a constellation of GPS satellites, which can be used forfacilitating location services such as navigation. The motion sensor5118 can utilize motion sensing technology such as an accelerometer, agyroscope, or other suitable motion sensing technology to detect motionof the communication device 5100 in three-dimensional space. Theorientation sensor 5120 can utilize orientation sensing technology suchas a magnetometer to detect the orientation of the communication device5100 (north, south, west, and east, as well as combined orientations indegrees, minutes, or other suitable orientation metrics).

The communication device 5100 can use the transceiver 5102 to alsodetermine a proximity to a cellular, WiFi, Bluetooth®, or other wirelessaccess points by sensing techniques such as utilizing a received signalstrength indicator (RSSI) and/or signal time of arrival (TOA) or time offlight (TOF) measurements. The controller 5106 can utilize computingtechnologies such as a microprocessor, a digital signal processor (DSP),programmable gate arrays, application specific integrated circuits,and/or a video processor with associated storage memory such as Flash,ROM, RAM, SRAM, DRAM or other storage technologies for executingcomputer instructions, controlling, and processing data supplied by theaforementioned components of the communication device 5100.

Other components not shown in FIG. 51 can be used in one or moreembodiments of the subject disclosure. For instance, the communicationdevice 5100 can include a slot for adding or removing an identity modulesuch as a Subscriber Identity Module (SIM) card or Universal IntegratedCircuit Card (UICC). SIM or UICC cards can be used for identifyingsubscriber services, executing programs, storing subscriber data, and soon.

In the subject specification, terms such as “store,” “storage,” “datastore,” data storage,” “database,” and substantially any otherinformation storage component relevant to operation and functionality ofa component, refer to “memory components,” or entities embodied in a“memory” or components comprising the memory. It will be appreciatedthat the memory components described herein can be either volatilememory or nonvolatile memory, or can comprise both volatile andnonvolatile memory, by way of illustration, and not limitation, volatilememory, non-volatile memory, disk storage, and memory storage. Further,nonvolatile memory can be included in read only memory (ROM),programmable ROM (PROM), electrically programmable ROM (EPROM),electrically erasable ROM (EEPROM), or flash memory. Volatile memory cancomprise random access memory (RAM), which acts as external cachememory. By way of illustration and not limitation, RAM is available inmany forms such as synchronous RAM (SRAM), dynamic RAM (DRAM),synchronous DRAM (SDRAM), double data rate SDRAM (DDR SDRAM), enhancedSDRAM (ESDRAM), Synchlink DRAM (SLDRAM), and direct Rambus RAM (DRRAM).Additionally, the disclosed memory components of systems or methodsherein are intended to comprise, without being limited to comprising,these and any other suitable types of memory.

Moreover, it will be noted that the disclosed subject matter can bepracticed with other computer system configurations, comprisingsingle-processor or multiprocessor computer systems, mini-computingdevices, mainframe computers, as well as personal computers, hand-heldcomputing devices (e.g., PDA, phone, smartphone, watch, tabletcomputers, netbook computers, etc.), microprocessor-based orprogrammable consumer or industrial electronics, and the like. Theillustrated aspects can also be practiced in distributed computingenvironments where tasks are performed by remote processing devices thatare linked through a communications network; however, some if not allaspects of the subject disclosure can be practiced on stand-alonecomputers. In a distributed computing environment, program modules canbe located in both local and remote memory storage devices.

Some of the embodiments described herein can also employ artificialintelligence (AI) to facilitate automating one or more featuresdescribed herein. For example, artificial intelligence can be used inoptional training controller 230 evaluate and select candidatefrequencies, modulation schemes, MIMO modes, and/or guided wave modes inorder to maximize transfer efficiency. The embodiments (e.g., inconnection with automatically identifying acquired cell sites thatprovide a maximum value/benefit after addition to an existingcommunication network) can employ various AI-based schemes for carryingout various embodiments thereof. Moreover, the classifier can beemployed to determine a ranking or priority of the each cell site of theacquired network. A classifier is a function that maps an inputattribute vector, x=(x1, x2, x3, x4, . . . , xn), to a confidence thatthe input belongs to a class, that is, f(x)=confidence (class). Suchclassification can employ a probabilistic and/or statistical-basedanalysis (e.g., factoring into the analysis utilities and costs) toprognose or infer an action that a user desires to be automaticallyperformed. A support vector machine (SVM) is an example of a classifierthat can be employed. The SVM operates by finding a hypersurface in thespace of possible inputs, which the hypersurface attempts to split thetriggering criteria from the non-triggering events. Intuitively, thismakes the classification correct for testing data that is near, but notidentical to training data. Other directed and undirected modelclassification approaches comprise, e.g., naïve Bayes, Bayesiannetworks, decision trees, neural networks, fuzzy logic models, andprobabilistic classification models providing different patterns ofindependence can be employed. Classification as used herein also isinclusive of statistical regression that is utilized to develop modelsof priority.

As will be readily appreciated, one or more of the embodiments canemploy classifiers that are explicitly trained (e.g., via a generictraining data) as well as implicitly trained (e.g., via observing UEbehavior, operator preferences, historical information, receivingextrinsic information). For example, SVMs can be configured via alearning or training phase within a classifier constructor and featureselection module. Thus, the classifier(s) can be used to automaticallylearn and perform a number of functions, including but not limited todetermining according to a predetermined criteria which of the acquiredcell sites will benefit a maximum number of subscribers and/or which ofthe acquired cell sites will add minimum value to the existingcommunication network coverage, etc.

As used in some contexts in this application, in some embodiments, theterms “component,” “system” and the like are intended to refer to, orcomprise, a computer-related entity or an entity related to anoperational apparatus with one or more specific functionalities, whereinthe entity can be either hardware, a combination of hardware andsoftware, software, or software in execution. As an example, a componentmay be, but is not limited to being, a process running on a processor, aprocessor, an object, an executable, a thread of execution,computer-executable instructions, a program, and/or a computer. By wayof illustration and not limitation, both an application running on aserver and the server can be a component. One or more components mayreside within a process and/or thread of execution and a component maybe localized on one computer and/or distributed between two or morecomputers. In addition, these components can execute from variouscomputer readable media having various data structures stored thereon.The components may communicate via local and/or remote processes such asin accordance with a signal having one or more data packets (e.g., datafrom one component interacting with another component in a local system,distributed system, and/or across a network such as the Internet withother systems via the signal). As another example, a component can be anapparatus with specific functionality provided by mechanical partsoperated by electric or electronic circuitry, which is operated by asoftware or firmware application executed by a processor, wherein theprocessor can be internal or external to the apparatus and executes atleast a part of the software or firmware application. As yet anotherexample, a component can be an apparatus that provides specificfunctionality through electronic components without mechanical parts,the electronic components can comprise a processor therein to executesoftware or firmware that confers at least in part the functionality ofthe electronic components. While various components have beenillustrated as separate components, it will be appreciated that multiplecomponents can be implemented as a single component, or a singlecomponent can be implemented as multiple components, without departingfrom example embodiments.

Further, the various embodiments can be implemented as a method,apparatus or article of manufacture using standard programming and/orengineering techniques to produce software, firmware, hardware or anycombination thereof to control a computer to implement the disclosedsubject matter. The term “article of manufacture” as used herein isintended to encompass a computer program accessible from anycomputer-readable device or computer-readable storage/communicationsmedia. For example, computer readable storage media can include, but arenot limited to, magnetic storage devices (e.g., hard disk, floppy disk,magnetic strips), optical disks (e.g., compact disk (CD), digitalversatile disk (DVD)), smart cards, and flash memory devices (e.g.,card, stick, key drive). Of course, those skilled in the art willrecognize many modifications can be made to this configuration withoutdeparting from the scope or spirit of the various embodiments.

In addition, the words “example” and “exemplary” are used herein to meanserving as an instance or illustration. Any embodiment or designdescribed herein as “example” or “exemplary” is not necessarily to beconstrued as preferred or advantageous over other embodiments ordesigns. Rather, use of the word example or exemplary is intended topresent concepts in a concrete fashion. As used in this application, theterm “or” is intended to mean an inclusive “or” rather than an exclusive“or”. That is, unless specified otherwise or clear from context, “Xemploys A or B” is intended to mean any of the natural inclusivepermutations. That is, if X employs A; X employs B; or X employs both Aand B, then “X employs A or B” is satisfied under any of the foregoinginstances. In addition, the articles “a” and “an” as used in thisapplication and the appended claims should generally be construed tomean “one or more” unless specified otherwise or clear from context tobe directed to a singular form.

Moreover, terms such as “user equipment,” “mobile station,” “mobile,”subscriber station,” “access terminal,” “terminal,” “handset,” “mobiledevice” (and/or terms representing similar terminology) can refer to awireless device utilized by a subscriber or user of a wirelesscommunication service to receive or convey data, control, voice, video,sound, gaming or substantially any data-stream or signaling-stream. Theforegoing terms are utilized interchangeably herein and with referenceto the related drawings.

Furthermore, the terms “user,” “subscriber,” “customer,” “consumer” andthe like are employed interchangeably throughout, unless contextwarrants particular distinctions among the terms. It should beappreciated that such terms can refer to human entities or automatedcomponents supported through artificial intelligence (e.g., a capacityto make inference based, at least, on complex mathematical formalisms),which can provide simulated vision, sound recognition and so forth.

As employed herein, the term “processor” can refer to substantially anycomputing processing unit or device comprising, but not limited tocomprising, single-core processors; single-processors with softwaremultithread execution capability; multi-core processors; multi-coreprocessors with software multithread execution capability; multi-coreprocessors with hardware multithread technology; parallel platforms; andparallel platforms with distributed shared memory. Additionally, aprocessor can refer to an integrated circuit, an application specificintegrated circuit (ASIC), a digital signal processor (DSP), a fieldprogrammable gate array (FPGA), a programmable logic controller (PLC), acomplex programmable logic device (CPLD), a discrete gate or transistorlogic, discrete hardware components or any combination thereof designedto perform the functions described herein. Processors can exploitnano-scale architectures such as, but not limited to, molecular andquantum-dot based transistors, switches and gates, in order to optimizespace usage or enhance performance of user equipment. A processor canalso be implemented as a combination of computing processing units.

As used herein, terms such as “data storage,” data storage,” “database,”and substantially any other information storage component relevant tooperation and functionality of a component, refer to “memorycomponents,” or entities embodied in a “memory” or components comprisingthe memory. It will be appreciated that the memory components orcomputer-readable storage media, described herein can be either volatilememory or nonvolatile memory or can include both volatile andnonvolatile memory.

What has been described above includes mere examples of variousembodiments. It is, of course, not possible to describe everyconceivable combination of components or methodologies for purposes ofdescribing these examples, but one of ordinary skill in the art canrecognize that many further combinations and permutations of the presentembodiments are possible. Accordingly, the embodiments disclosed and/orclaimed herein are intended to embrace all such alterations,modifications and variations that fall within the spirit and scope ofthe appended claims. Furthermore, to the extent that the term “includes”is used in either the detailed description or the claims, such term isintended to be inclusive in a manner similar to the term “comprising” as“comprising” is interpreted when employed as a transitional word in aclaim.

In addition, a flow diagram may include a “start” and/or “continue”indication. The “start” and “continue” indications reflect that thesteps presented can optionally be incorporated in or otherwise used inconjunction with other routines. In this context, “start” indicates thebeginning of the first step presented and may be preceded by otheractivities not specifically shown. Further, the “continue” indicationreflects that the steps presented may be performed multiple times and/ormay be succeeded by other activities not specifically shown. Further,while a flow diagram indicates a particular ordering of steps, otherorderings are likewise possible provided that the principles ofcausality are maintained.

As may also be used herein, the term(s) “operably coupled to”, “coupledto”, and/or “coupling” includes direct coupling between items and/orindirect coupling between items via one or more intervening items. Suchitems and intervening items include, but are not limited to, junctions,communication paths, components, circuit elements, circuits, functionalblocks, and/or devices. As an example of indirect coupling, a signalconveyed from a first item to a second item may be modified by one ormore intervening items by modifying the form, nature or format ofinformation in a signal, while one or more elements of the informationin the signal are nevertheless conveyed in a manner than can berecognized by the second item. In a further example of indirectcoupling, an action in a first item can cause a reaction on the seconditem, as a result of actions and/or reactions in one or more interveningitems.

Although specific embodiments have been illustrated and describedherein, it should be appreciated that any arrangement which achieves thesame or similar purpose may be substituted for the embodiments describedor shown by the subject disclosure. The subject disclosure is intendedto cover any and all adaptations or variations of various embodiments.Combinations of the above embodiments, and other embodiments notspecifically described herein, can be used in the subject disclosure.For instance, one or more features from one or more embodiments can becombined with one or more features of one or more other embodiments. Inone or more embodiments, features that are positively recited can alsobe negatively recited and excluded from the embodiment with or withoutreplacement by another structural and/or functional feature. The stepsor functions described with respect to the embodiments of the subjectdisclosure can be performed in any order. The steps or functionsdescribed with respect to the embodiments of the subject disclosure canbe performed alone or in combination with other steps or functions ofthe subject disclosure, as well as from other embodiments or from othersteps that have not been described in the subject disclosure. Further,more than or less than all of the features described with respect to anembodiment can also be utilized.

What is claimed is:
 1. A method, comprising: generating, by a voltagewaveform generator, an alternating voltage periodic waveform directed toa winding coupled to a magnetic core of an inductive power supply toregulate an alternating magnetic flux in the magnetic core, wherein themagnetic core comprises a first portion and a second portion, whereinthe first portion of the magnetic core is separable from the secondportion of the magnetic core, wherein the magnetic core is magneticallycoupled to a conductor that conducts an alternating current that causesa portion of the alternating magnetic flux, wherein the alternatingmagnetic flux causes a coupling force between the first portion of themagnetic core and the second portion of the magnetic core, and whereinthe alternating voltage periodic waveform is generated by selectivelyenabling one or more switches coupled to a storage device; detecting asignal to reduce the coupling force between the first portion of themagnetic core and the second portion of the magnetic core; andresponsive to the signal, modifying the regulation of the alternatingmagnetic flux to reduce the coupling force between the first portion ofthe magnetic core and the second portion of the magnetic core.
 2. Themethod of claim 1, wherein the modifying comprises configuring at leastone of the one or more switches to modify the regulation of thealternating magnetic flux.
 3. The method of claim 2, wherein theconfiguring the at least one of the one or more switches causes thewinding to be short circuited.
 4. The method of claim 1, wherein themodifying the regulation of the alternating magnetic flux comprisesshort circuiting the winding.
 5. The method of claim 1, wherein themodifying the regulation of the alternating magnetic flux comprisesterminating a directing of the alternating voltage periodic waveform tothe winding.
 6. The method of claim 1, wherein, during a first period ofthe alternating voltage periodic waveform, the alternating magnetic fluxvaries, as a function of time, in accordance with a first pattern ofvariations, and wherein the method further comprises configuring, by aprocessor, the one or more switches in accordance with a configurationduring at least part of a second period of the alternating voltageperiodic waveform, wherein the configuration causes the alternatingmagnetic flux to vary, as a function of time, during the second period,in accordance with a second pattern of variations, and wherein thesecond pattern of variations is different from the first pattern ofvariations.
 7. The method of claim 6, wherein the second pattern ofvariations comprises a portion of the second period during which thealternating magnetic flux is negligible, wherein a duration of theportion of the second period is at least a quarter of a duration of thesecond period.
 8. The method of claim 6, wherein the configuration ofthe one or more switches results in substantially a short-circuit acrossthe winding.
 9. The method of claim 6, wherein the configuration of theone or more switches results in a known resistance being applied acrossthe winding.
 10. The method of claim 6, further comprising measuring, bythe processor, a characteristic of the alternating current during thesecond period.
 11. The method of claim 10, wherein the characteristiccomprises an amplitude of the alternating current flowing through theconductor that conducts the alternating current.
 12. The method of claim11, wherein the amplitude of the alternating current is determined bymeasuring a voltage across a first switch of the one or more switches,and by determining an impedance of the first switch while in an openstate.
 13. The method of claim 10, wherein the characteristic comprisesa phase of the alternating current.
 14. The method of claim 13, furthercomprising adjusting, by the processor, a phase of the alternatingvoltage periodic waveform according to the phase of the alternatingcurrent.
 15. The method of claim 10, further comprising adjusting, bythe processor, responsive to the measuring, selectively reconfiguringthe one or more switches to continue regulating the alternating magneticflux in the magnetic core.
 16. An inductive power supply, comprising: amagnetic core that facilitates coupling to a conductor that conducts analternating current; a winding wrapped around a cavity of the magneticcore; a storage device; one or more switches coupled to the winding andthe storage device; a processor; and a memory that stores executableinstructions that, when executed by the processor, facilitateperformance of operations, the operations comprising: generating, byselectively enabling the one or more switches coupled to the storagedevice, an alternating voltage periodic waveform directed to the windingcoupled to the magnetic core to regulate an alternating magnetic flux inthe magnetic core, wherein the magnetic core comprises a first portionand a second portion, wherein the first portion of the magnetic core isseparable from the second portion of the magnetic core, wherein themagnetic core is magnetically coupled to the conductor that conducts thealternating current that causes a portion of the alternating magneticflux, and wherein the alternating magnetic flux causes a coupling forcebetween the first portion of the magnetic core and the second portion ofthe magnetic core; receiving a signal to reduce the coupling forcebetween the first portion of the magnetic core and the second portion ofthe magnetic core; and responsive to the signal, modifying theregulation of the alternating magnetic flux to reduce the coupling forcebetween the first portion of the magnetic core and the second portion ofthe magnetic core.
 17. The inductive power supply of claim 16, whereinthe modifying comprises causing the winding to be short circuited.
 18. Amethod, comprising: generating an alternating voltage periodic waveformthat is supplied to a winding coupled to a magnetic core of an inductivepower supply to regulate an alternating magnetic flux in the magneticcore, wherein the magnetic core comprises a first portion and a secondportion, wherein the first portion of the magnetic core is separablefrom the second portion of the magnetic core, wherein the magnetic coreis magnetically coupled to a conductor that conducts an alternatingcurrent that causes a portion of the alternating magnetic flux, whereinthe alternating magnetic flux causes a coupling force between the firstportion of the magnetic core and the second portion of the magneticcore; and responsive to detecting a signal, modifying the regulation ofthe alternating magnetic flux to reduce the coupling force between thefirst portion of the magnetic core and the second portion of themagnetic core.
 19. The method of claim 18, wherein the modifying theregulation of the alternating magnetic flux comprises short circuitingthe winding.
 20. The method of claim 18, wherein the modifying theregulation of the alternating magnetic flux comprises terminating asupply of the alternating voltage periodic waveform to the winding.